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rev. 0 information furnished by analog devices is believed to be accurate and reliable. however, no responsibility is assumed by analog devices for its use, nor for any infringements of patents or other rights of third parties that may result from its use. no license is granted by implication or otherwise under any patent or patent rights of analog devices. trademarks and registered trademarks are the property of their respective companies. one technology way, p.o. box 9106, norwood, ma 02062-9106, u.s.a. tel: 781/329-4700 www.analog.com fax: 781/326-8703 ?2003 analog devices, inc. all rights reserved. AD9887A dual interface for flat panel displays features analog interface 170 msps maximum conversion rate programmable analog bandwidth 0.5 v to 1.0 v analog input range 500 ps p-p pll clock jitter at 170 msps 3.3 v power supply full sync processing midscale clamping 4:2:2 output format mode digital interface dvi 1.0 compatible interface 170 mhz operation (2 pixel/clock mode) high skew tolerance of 1 full input clock sync detect for ?ot plugging supports high bandwidth digital content protection applications rgb graphics processing lcd monitors and projectors plasma display panels scan converters micro displays digital tvs functional block diagram hsync coast clamp ckinv ckext filt vsync serial register and power management scl sda a 1 a 0 2 datack hsout vsout sogout rx0+ rx0 rx1+ rx1 rx2+ rx2 rxc+ rxc r term dvi receiver 8 8 8 r outa r outb 8 8 8 g outa g outb 8 8 8 b outa b outb 2 datack de AD9887A digital interface r outa r outb g outa g outb b outa b outb hsout vsout sogou t de datack 8 sync processing and clock generation clamp r ain clamp g ain clamp b ain a/d 8 8 8 r outa r outb a/d 8 8 8 g outa g outb a/d 8 8 8 b outa b outb analog interface s cdt refin ref refout ddcscl ddcsda mcl mda hdcp sogin m u x e s 8 8 8 8 8 2 hsout vsout general description the AD9887A offers designers the flexibility of an analog inter face and digital visual interface (dvi) receiver integrated on a single chip. also included is support for high bandwidth digital content protection (hdcp). the AD9887A is software and pin-to-pin compatible with the ad9887. analog interface the AD9887A is a complete 8-bit 170 msps monolithic analog interface optimized for capturing rgb graphics signals from personal computers and workstations. its 170 msps encode rate capability and full-power analog bandwidth of 330 mhz supports resolutions up to uxga (1600 1200 at 60 hz). the analog interface includes a 170 mhz triple adc with internal 1.25 v reference, a phase-locked loop (pll), and pro- grammable gain, offset, and clamp control. the user provides only a 3.3 v power supply, analog input, and hsync. three- state cmos outputs may be powered from 2.5 v to 3.3 v. the AD9887A s on-chip pll generates a pixel clock from hsync. pixel clock output frequencies range from 12 mhz to 170 mhz. pll clock jitter is typically 500 ps p-p at 170 msps. the AD9887A also offers full sync processing for composite sync and sync-on-green (sog) applications. digital interface the AD9887A contains a dvi 1.0 compatible receiver and supports display resolutions up to uxga (1600 1200 at 60 hz). the receiver operates with true color (24-bit) panels in 1 or 2 pixel(s)/clock mode and features an intrapair skew tolerance of up to one full clock cycle. with the inclusion of hdcp, displays may now receive encrypted video content. the AD9887A allows for authentication of a video receiver, decryption of encoded data at the receiver, and renewability of that authentication during transmission as specified by the hdcp v1.0 protocol. fabricated in an advanced cmos process, the AD9887A is provided in a 160-lead mqfp surface-mount plastic package and is specified over the 0 c to 70 c temperature range.
rev. 0 ? AD9887A table of contents features . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 1 applications . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 1 functional block diagram . . . . . . . . . . . . . . . . . 1 general description . . . . . . . . . . . . . . . . . . . . . . . . . 1 analog interface . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 1 digital interface . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 1 specifications . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 4 analog interface . . . . . . . . . . . . . . . . . . . . . . . . . . . . 4 digital interface . . . . . . . . . . . . . . . . . . . . . . . . . . . . 7 absolute maximum ratings . . . . . . . . . . . . . . . . . 7 explanation of test levels . . . . . . . . . . . . . . . . . 7 ordering guide . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 7 pin configuration . . . . . . . . . . . . . . . . . . . . . . . . . . . 8 descriptions of pins shared between analog and digital interfaces . . . . . . . . . . . . 10 serial port (2-wire) . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 10 data outputs . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 10 data clock outputs . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 10 various . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 10 scan function . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 10 pin function details (analog interface) . . 11 inputs . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 11 outputs . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 13 power supply . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 13 theory of operation (interface detection)13 active interface detection and selection . . . . . . . . . . . . . 13 power management . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 14 theory of operation and design guide (analog interface) . . . . . . . . . . . . . . . . . . . . . . . . . 15 general description . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 15 input signal handling . . . . . . . . . . . . . . . . . . . . . . . . . . . 15 hsync, vsync inputs . . . . . . . . . . . . . . . . . . . . . . . . . 15 serial control port . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 15 output signal handling . . . . . . . . . . . . . . . . . . . . . . . . . . 15 clamping . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 15 rgb clamping . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 15 yuv clamping . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 16 gain and offset control . . . . . . . . . . . . . . . . . . . . . . . . . 16 sync-on-green . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 16 clock generation . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 17 scan function . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 19 alternate pixel sampling mode . . . . . . . . . . . . . . . . . . . . 19 timing (analog interface) . . . . . . . . . . . . . . . . . . . . . . . . 20 hsync timing . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 20 coast timing . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 20 digital interface pin descriptions . . . . . . . . 25 digital video data inputs . . . . . . . . . . . . . . . . . . . . . . . . 25 digital clock inputs . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 25 termination control . . . . . . . . . . . . . . . . . . . . . . . . . . . . 25 outputs . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 25 power supply . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 25 theory of operation (digital interface) . . 25 capturing of the encoded data . . . . . . . . . . . . . . . . . . . . 25 data frames . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 25 special characters . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 25 channel resynchronization . . . . . . . . . . . . . . . . . . . . . . . 25 data decoder . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 25 hdcp . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 26 general timing diagrams (digital interface) . . . . . . . . . . . . . . . . . . . . . . . . . 27 timing mode diagrams (digital interface) 27 2-wire serial register map . . . . . . . . . . . . . . . . . . . . . . . . . 28 2-wire serial control register detail . . . . . 32 chip identification . . . . . . . . . . . . . . . . . . . . . . . . . 32 pll divider control . . . . . . . . . . . . . . . . . . . . . . . . 32 clock generator control . . . . . . . . . . . . . . . . . 32 clamp timing . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 32 input gain . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 33 input offset . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 33 mode control 1 . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 33 mode control 2 . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 35 sync detection and control . . . . . . . . . . . . . . 36 digital control . . . . . . . . . . . . . . . . . . . . . . . . . . . . 38 control bits . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 38 2-wire serial control port . . . . . . . . . . . . . . . . . . . . . . . . 39 data transfer via serial interface . . . . . . . . . . . . . . . . . . . 39 serial interface read/write examples . . . . . . . . . . . . . . . 40 theory of operation (sync processing) . . . . 40 sync stripper . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 40 sync seperator . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 40 pcb layout recommendations . . . . . . . . . . . . . 41 analog interface inputs . . . . . . . . . . . . . . . . . . . . . . . . . . 41 digital interface inputs . . . . . . . . . . . . . . . . . . . . . . . . . . 41 power supply bypassing . . . . . . . . . . . . . . . . . . . . . . . . . 42 pll . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 42 outputs (both data and clocks) . . . . . . . . . . . . . . . . . . . 42 digital inputs . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 42 voltage reference . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 42 outline dimensions . . . . . . . . . . . . . . . . . . . . . . . . . 43 table index table i. complete pinout list . . . . . . . . . . . . . . . . . . . . . . . . 9 table ii. analog interface pin list . . . . . . . . . . . . . . . . . . . 11 table iii. interface selection controls . . . . . . . . . . . . . . . . 14 table iv. power-down mode descriptions . . . . . . . . . . . . . 14 table v. vco frequency ranges . . . . . . . . . . . . . . . . . . . . 17 table vi. charge pump current/control bits . . . . . . . . . . . 17 table vii. recommended vco range and charge pump current settings for standard display formats . . . . . . . . . . 18 table viii. digital interface pin list . . . . . . . . . . . . . . . . . . 24 table ix. control register map . . . . . . . . . . . . . . . . . . . . . 28 table x. vco ranges . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 32 table xi. charge pump currents . . . . . . . . . . . . . . . . . . . . 32 table xii. channel mode settings . . . . . . . . . . . . . . . . . . . 33 table xiii. output mode settings . . . . . . . . . . . . . . . . . . . 33 table xiv. output port settings . . . . . . . . . . . . . . . . . . . . . 33 table xv. hsync output polarity settings . . . . . . . . . . . 34 table xvi. vsync output polarity settings . . . . . . . . . . . 34 table xvii. hsnyc input polarity settings . . . . . . . . . . . 34 table xviii. coast input polarity settings . . . . . . . . . . . 34 table xix. clamp input signal source settings . . . . . . . . . 34 table xx. clamp input signal polarity settings . . . . . . . 34 table xxi. external clock select settings . . . . . . . . . . . . . 34 table xxii. red clamp select settings . . . . . . . . . . . . . . . 35 table xxiii. green clamp select settings . . . . . . . . . . . . . 35 table xxiv. blue clamp select settings . . . . . . . . . . . . . . 35 table xxv. clock output invert settings . . . . . . . . . . . . . . 35 table xxvi. pix select settings . . . . . . . . . . . . . . . . . . . . . 35 table xxvii. output drive strength settings . . . . . . . . . . 35 table xxviii. power-down output settings . . . . . . . . . . . 35
rev. 0 AD9887A ? table index (continued) table xxix. sync detect polarity settings . . . . . . . . . . . . . 35 table xxx. hsync detection results . . . . . . . . . . . . . . . 36 table xxxi. sync-on-green detection results . . . . . . . . . 36 table xxxii. vsync detection results . . . . . . . . . . . . . . 36 table xxxiii. digital interface clock detection results . . 36 table xxxiv. active interface results . . . . . . . . . . . . . . . . 36 table xxxv. active hsync results . . . . . . . . . . . . . . . . . 36 table xxxvi. active vsync results . . . . . . . . . . . . . . . . 37 table xxxvii. active interface override settings . . . . . . . 37 table xxxviii. active interface select settings . . . . . . . . . 37 table xxxix. active hsync override settings . . . . . . . . . . 37 table xl. active hsync select settings . . . . . . . . . . . . . . 37 table xli. active vsync override settings . . . . . . . . . . . 37 table xlii. active vsync select settings . . . . . . . . . . . . . 37 table xliii. coast select settings . . . . . . . . . . . . . . . . . 37 table xliv. power-down settings . . . . . . . . . . . . . . . . . . . 37 table xlv. scan enable settings . . . . . . . . . . . . . . . . . . . . 38 table xlvi. coast input polarity override settings . . . . . . 38 table xlvii. hsync input polarity override settings . . . 38 table xlviii. detected hsync input polarity status . . . 38 table xlix. detected vsync input polarity status . . . . . 38 table l. detected coast input polarity status . . . . . . . . . . 38 table li. 4:2:2 input/output configuration . . . . . . . . . . . . 39 table lii. 4:2:2 output mode select . . . . . . . . . . . . . . . . . 39 table liii. serial port addresses . . . . . . . . . . . . . . . . . . . . 39 table liv. control of the sync block muxes via the serial register . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 40
rev. 0 ? AD9887A?pecifications test AD9887Aks-100 AD9887Aks-140 AD9887Aks-170 parameter temp level min typ max min typ max min typ max unit resolution 8 8 8 bits dc accuracy differential nonlinearity 25 ci 0.5 +1.15/ C 1.0 0.5 +1.25/ C 1.0 0.8 +1.25/ C 1.0 lsb full vi +1.15/ C 1.0 +1.25/ C 1.0 +1.50/ C 1.0 lsb integral nonlinearity 25 ci 0.5 1.40 0.5 1.4 1.0 2.25 lsb full vi 1.75 2.5 2.75 lsb no missing codes 25 ci guaranteed guaranteed guaranteed analog input input voltage range minimum full vi 0.5 0.5 0.5 v p-p maximum full vi 1.0 1.0 1.0 v p-p gain tempco 25 cv 135 150 150 ppm/ c input bias current 25 civ 111 a full iv 1 1 1 a input full-scale matching full vi 8.0 8.0 8.0 % fs offset adjustment range full vi 43 48 53 43 48 53 43 48 53 % fs reference output output voltage full v 1.3 1.3 1.3 v temperature coef ? cient full v 90 90 90 ppm/ c switching performance 1 maximum conversion rate full vi 100 140 170 msps minimum conversion rate full iv 10 10 10 msps clock to data skew, t skew full iv C 1.5 +2.5 C 1.5 +2.5 C 1.5 +2.5 ns serial port timing t buff full vi 4.7 4.7 4.7 s t stah full vi 4.0 4.0 4.0 s t dho full vi 0 0 0 s t dal full vi 4.7 4.7 4.7 s t dah full vi 4.0 4.0 4.0 s t dsu full vi 250 250 250 ns t stasu full vi 4.7 4.7 4.7 s t stosu full vi 4.0 4.0 4.0 s hsync input frequency full iv 15 110 15 110 15 110 khz maximum pll clock rate full vi 100 140 170 mhz minimum pll clock rate full iv 12 12 12 mhz pll jitter 25 civ 500 700 2 440 650 3 370 500 4 ps p-p full iv 1000 2 700 3 700 4 ps p-p sampling phase tempco full iv 10 10 10 ps/ c digital inputs input voltage, high (v ih ) full vi 2.6 2.6 2.6 v input voltage, low (v il ) full vi 0.8 0.8 0.8 v input current, high (v ih ) full iv C 1.0 C 1.0 C 1.0 a input current, low (v il ) full iv +1.0 +1.0 +1.0 a input capacitance 25 cv 333pf digital outputs output voltage, high (v oh ) full vi 2.4 2.4 2.4 v output voltage, low (v ol ) full vi 0.4 0.4 0.4 v duty cycle datack, datack full iv 45 55 60 45 55 60 45 55 65 % output coding binary binary binary analog interface (v d = 3.3 v, v dd = 3.3 v, adc clock = maximum conversion rate, unless otherwise noted.)
rev. 0 AD9887A ? test AD9887Aks-100 AD9887Aks-140 AD9887Aks-170 parameter temp level min typ max min typ max min typ max unit power supply v d supply voltage full iv 3.15 3.3 3.45 3.15 3.3 3.45 3.15 3.3 3.45 v v dd supply voltage full iv 2.2 3.3 3.45 2.2 3.3 3.45 2.2 3.3 3.45 v p vd supply voltage full iv 3.15 3.3 3.45 3.15 3.3 3.45 3.15 3.3 3.45 v i d supply current (v d )25 cv 140 155 230 ma i dd supply current (v dd ) 5 25 cv 34 48 55 ma ip vd supply current (p vd )25 cv 15 16 60 ma total supply current 5 full vi 300 330 335 360 345 390 ma power-down supply current full vi 90 120 90 120 90 120 ma dynamic performance analog bandwidth, full power 25 cv 330 330 330 mhz transient response 25 cv 222ns overvoltage recovery time 25 cv 1.5 1.5 1.5 ns signal-to-noise ratio (snr) 6 25 cv 46 46 45 db f in = 40.7 mhz crosstalk full v 60 60 60 dbc thermal characteristics ja junction-to-ambient 7 v37 3 737 c/w thermal resistance notes 1 drive strength = 11. 2 vco range = 01, charge pump current = 001, pll divider = 1693. 3 vco range = 10, charge pump current = 110, pll divider = 1600. 4 vco range = 11, charge pump current = 110, pll divider = 2159. 5 demux = 1, datack and datack load = 10 pf, data load = 5 pf. 6 using external pixel clock. 7 simulated typical performance with package mounted to a 4-layer board. speci ? cations subject to change without notice.
rev. 0 ? AD9887A?pecifications digital interface (v d = 3.3 v, v dd = 3.3 v, clock = maximum.) test AD9887Aks parameter conditions temp level min typ max unit resolution 8b its dc digital i/o specifications high level input voltage (v ih ) full vi 2.6 v low level input voltage (v il ) full vi 0.8 v high level output voltage (v oh ) full vi 2.4 v low level output voltage (v ol ) full vi 0.4 v input clamp voltage (v cinl )(i cl = C 18 ma) iv gnd C 0.8 v input clamp voltage (v cipl )(i cl = +18 ma) iv v dd + 0.8 v output clamp voltage (v conl )(i cl = C 18 ma) iv gnd C 0.8 v output clamp voltage (v copl )(i cl = +18 ma) iv v dd + 0.8 v output leakage current (i ol )(h igh impedance) full iv C 10 +10 a dc specifications output high drive output drive = high full iv 13 ma (i ohd ) (v out = v oh ) output drive = med full iv 8 ma output drive = low full iv 5 ma output drive = high full iv C 9ma (i old ) (v out = v ol ) output drive = med full iv C 7ma output drive = low full iv C 5ma output drive = high full iv 25 ma (v ohc ) (v out = v oh ) output drive = med full iv 12 ma output drive = low full iv 8 ma datack low drive output drive = high full iv C 25 ma (v olc ) (v out = v ol ) output drive = med full iv C 19 ma output drive = low full iv C 8ma differential input voltage single-ended amplitude full iv 75 800 mv power supply v d supply voltage full iv 3.15 3.3 3.45 v v dd supply voltage minimum value for 2 pixels per clock mode full iv 2.2 3.3 3.45 v p vd supply voltage full iv 3.15 3.3 3.45 v i d supply current 1 25 c v 350 ma i dd supply current 1, 2 25 c v40 ma ip vd supply current 1 25 c iv 130 ma total supply current with hdcp 1, 2 vi 520 560 ma ac specifications intrapair (+ to C ) differential input skew (t dps ) full iv 360 ps channel-to-channel differential input skew (t ccs ) full iv 1.0 clock period low-to-high transition time for data and output drive = high; c l = 10 pf full iv 2.5 ns controls (d lht ) output drive = med; c l = 7 pf full iv 3.1 ns output drive = low; c l = 5 pf full iv 5.4 ns low-to-high transition time for datack (d lht ) output drive = high; c l = 10 pf full iv 1.2 ns output drive = med; c l = 7 pf full iv 1.6 ns output drive = low; c l = 5 pf full iv 2.3 ns high-to-low transition time for data (d hlt ) output drive = high; c l = 10 pf full iv 2.6 ns output drive = med; c l = 7 pf full iv 3.0 ns output drive = low; c l = 5 pf full iv 3.7 ns
rev. 0 AD9887A ? caution esd (electrostatic discharge) sensitive device. electrostatic charges as high as 4000 v readily accumulate on the human body and test equipment and can discharge without detection. although the AD9887A features proprietary esd protection circuitry, permanent damage may occur on devices subjected to high energy electrostatic discharges. therefore, proper esd precautions are recommended to avoid performance degradation or loss of functionality. absolute maximum ratings * v d . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 3.6 v v dd . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 3.6 v analog inputs . . . . . . . . . . . . . . . . . . . . . . . . . . . . v d to 0.0 v vref in . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . v d to 0.0 v digital inputs . . . . . . . . . . . . . . . . . . . . . . . . . . . 5 v to 0.0 v digital output current . . . . . . . . . . . . . . . . . . . . . . . . . 20 ma operating temperature . . . . . . . . . . . . . . . . . . C 25 c to +85 c storage temperature . . . . . . . . . . . . . . . . . . C 65 c to +150 c maximum junction temperature . . . . . . . . . . . . . . . . . 150 c maximum case temperature . . . . . . . . . . . . . . . . . . . . 150 c * stresses above those listed under absolute maximum ratings may cause perma- nent damage to the device. this is a stress rating only; functional operation of the device at these or any other conditions outside of those indicated in the operation sections of this speci ? cation is not implied. exposure to absolute maximum ratings for extended periods may affect device reliability. ordering guide max speed (mhz) temperature package package model analog dvi range description option AD9887Aks-170 170 170 0 c to 70 cm etric quad flatpack s-160 AD9887Aks-140 140 140 0 c to 70 cm etric quad flatpack s-160 AD9887Aks-100 100 100 0 c to 70 cm etric quad flatpack s-160 AD9887A/pcb 25 ce valuation board test AD9887Aks parameter conditions temp level min typ max unit ac specifications (continued) high-to-low transition time for datack (d hlt ) output drive = high; c l =10 pf full iv 1.4 ns output drive = med; c l = 7 pf full iv 1.6 ns output drive = low; c l = 5 pf full iv 2.4 ns clock to data skew, t skew 3 full iv 0 4.0 ns duty cycle, datack, datack 3 full iv 45 55 % of period high datack frequency (f cip ) (1 pixel/clock) full vi 20 140 mhz datack frequency (f cip ) (2 pixels/clock) full iv 10 85 mhz notes 1 the typical pattern contains a gray scale area, output drive = high. 2 datack and datack load = 10 pf, data load = 5 pf, hdcp disabled. 3 drive strength = 11 specifications subject to change without notice. explanation of test levels test level explanation i 100% production tested. ii 100% production tested at 25 c and sample tested at speci ? ed temperatures. iii sample tested only. iv parameter is guaranteed by design and charac- terization testing. v parameter is a typical value only. vi 100% production tested at 25 c; guaranteed by design and characterization testing.
rev. 0 ? AD9887A pin configuration red b<0> red b<1> red b<2> red b<3> red b<4> red b<5> red b<6> red b<7> gnd v dd red a<0> red a<1> red a<2> red a<3> red a<4> red a<5> red a<6> red a<7> gnd v dd sogout hsout vsout de s cdt datack datack gnd v dd gnd gnd scan in gnd v d refout v d v d gnd gnd 160 159 158 157 156 155 154 153 152 151 150 149 147 146 145 144 143 142 141 140 139 138 148 137 136 135 133 132 131 130 129 128 134 127 126 125 123 122 121 124 gnd gnd v dd gnd scan out ctl0 ctl1 ctl2 mcl scan clk v d gnd r term v d v d rx2+ rx2 gnd rx1+ rx1 gnd rx0+ rx0 gnd rxc+ rxc v d v d gnd v d mda ddcsda gnd pv d gnd pv d filt pv d gnd 53 54 55 56 57 58 59 60 61 62 41 42 43 44 45 46 47 48 49 50 51 52 63 64 65 66 68 69 70 71 72 67 73 74 75 76 78 79 80 77 5 4 3 2 7 6 9 8 1 14 13 12 16 15 17 10 19 18 23 22 21 20 25 24 27 26 29 28 32 31 30 34 33 36 35 40 39 38 37 v dd gnd green a<7> green a<6> green a<5> green a<4> green a<3> green a<2> green a<1> green a<0> v dd gnd green b<7> green b<6> green b<5> green b<4> green b<3> green b<2> green b<1> green b<0> v dd gnd blue a<7> blue a<6> blue a<5> blue a<4> blue a<3> blue a<2> blue a<1> blue a<0> v dd gnd blue b<7> blue b<6> blue b<5> blue b<4> blue b<3> blue b<2> blue b<1> blue b<0> r midsc v r ain r clamp v v d gnd v d v d gnd gnd g midsc v g ain g clamp v sogin v d gnd v d v d gnd gnd b midsc v b ain b clamp v v d gnd v d gnd ckinv clamp sda scl a0 a1 pv d pv d gnd gnd coast ckext hsync vsync 104 119 120 114 115 116 117 112 113 111 118 109 110 105 106 107 108 102 103 100 101 98 99 95 96 97 93 94 91 92 90 87 88 89 86 84 85 82 83 81 pin 1 identifier AD9887A top view (not to scale) 11 ddcscl refin
rev. 0 AD9887A ? table i. complete pinout list pin pin pin type mnemonic function value number interface analog video r ain analog input for converter r 0.0 v to 1.0 v 119 analog inputs g ain analog input for converter g 0.0 v to 1.0 v 110 analog b ain analog input for converter b 0.0 v to 1.0 v 100 analog external hsync horizontal sync input 3.3 v cmos 82 analog sync/clock vsync vertical sync input 3.3 v cmos 81 analog inputs sogin input for sync-on-green 0.0 v to 1.0 v 108 analog clamp clamp input (external clamp signal) 3.3 v cmos 93 analog coast pll coast signal input 3.3 v cmos 84 analog ckext external pixel cl ock input (to bypass the pll) to v dd or ground 3.3 v cmos 83 analog ckinv adc sampling clock invert 3.3 v cmos 94 analog sync outputs hsout hsync output clock (phase-aligned with datack) 3.3 v cmos 139 both vsout vsync output clock 3.3 v cmos 138 both sogout composite sync 3.3 v cmos 140 analog voltage refout internal reference output (bypass with 0.1 f to ground) 1.25 v 126 analog reference refin reference input (1.25 v 10%) 1.25 v 10% 125 analog clamp voltages r midsc vr ed channel midscale clamp voltage output 120 analog r clamp vr ed channel midscale clamp voltage input 0.0 v to 0.75 v 118 analog g midsc vg reen channel midscale clamp voltage output 111 analog g clamp vg reen channel midscale clamp voltage input 0.0 v to 0.75 v 109 analog b midsc vb lue channel midscale clamp voltage output 101 analog b clamp vb lue channel midscale clamp voltage input 0.0 v to 0.75 v 99 analog pll filter filt connection for external filter components for internal pll 78 analog power supply v d analog power supply 3.3 v 10% both v dd output power supply 3.3 v 10% both pv d pll power supply 3.3 v 10% both gnd ground 0 v both serial port sda serial port data i/o 3.3 v cmos 92 both (2-wire scl serial port data clock (100 khz max) 3.3 v cmos 91 both serial interface) a0 serial port address input 1 3.3 v cmos 90 both a1 serial port address input 2 3.3 v cmos 89 both data outputs red b[7:0] port b/odd outputs of converter red, bit 7 is the msb 3.3 v cmos 153 C 160 both green b[7:0] port b/ odd outputs of converter green, b it 7 is the msb 3.3 v cmos 13 C 20 both blue b[7:0] port b/odd outputs of converter blue, bit 7 is the msb 3.3 v cmos 33 C 40 both red a[7:0] port a/even outputs of converter red, bit 7 is the msb 3.3 v cmos 143 C 150 both green a[7:0] port a/even outputs of converter green, bit 7 is the msb 3.3 v cmos 3 C 10 both blue a[7:0] port a/even outputs of converter blue, bit 7 is the msb 3.3 v cmos 23 C 30 both data clock datack data output clock for the analog and digital interface 3.3 v cmos 134 both outputs datack data output clock complement for the analog interface only 3.3 v cmos 135 both sync detect s cdt sync detect output 3.3 v cmos 136 both scan function scan in input for scan function 3.3 v cmos 129 both scan out output for scan function 3.3 v cmos 45 both scan clk clock for scan function 3.3 v cmos 50 both digital video rx0+ digital input channel 0 true 62 digital data inputs rx0 C digital input channel 0 complement 63 digital rx1+ digital input channel 1 true 59 digital rx1 C digital input channel 1 complement 60 digital rx2+ digital input channel 2 true 56 digital rx2 C digital input channel 2 complement 57 digital
rev. 0 ?0 AD9887A p in pin pin type mnemonic function value number interface digital video rxc+ digital data clock true 65 digital clock inputs rxc C digital data clock complement 66 digital data enable de data enable 3.3 v cmos 137 digital control bits ctl[0:2] decoded control bits 3.3 v cmos 46 C 48 digital r term r term sets internal termination resistance 53 digital hdcp ddcscl hdcp slave serial port data clock 3.3 v cmos 73 digital ddcsda hdcp slave serial port data i/o 3.3 v cmos 72 digital mcl hdcp master serial port data clock 3.3 v cmos 49 digital mda hdcp master serial port data i/o 3.3 v cmos 71 digital descriptions of pins shared between analog and digital interfaces hsout horizontal sync output a reconstructed and phase-aligned version of the video hsync. the polarity of this output can be controlled via a serial bus bit. in analog interface mode, the placement and duration are variable. in digital interface mode, the placement and duration are set by the graphics transmitter. vsout vertical sync output the separated vsync from a composite signal or a direct pass through of the vsync input. the polarity of this output can be con- trolled via a serial bus bit. the placement and duration in all modes is set by the graphics transmitter. serial port (2-wire) sda serial port data i/o scl serial port data clock a0 serial port address input 1 a1 serial port address input 2 for a full description of the 2-wire serial regis- ter and how it works, refer to the control register section. data outputs red a data output, red channel, port a/even red b data output, red channel, port b/odd green a data output, green channel, port a/even green b data output, green channel, port b/odd blue a data output, blue channel, port a/even blue b data output, blue channel, port b/odd the main data outputs. bit 7 is the msb. these outputs are shared between the two interfaces and behave according to which interface is active. refer to the sections on the two interfaces for more information on how these outputs behave. data clock outputs datack data output clock datack data output clock complement just like the data outputs, the data clock outputs are shared between the two interfaces. they also behave differently depending on which interface is active. refer to the sections on the two interfaces to determine how these pins behave. various s cdt chip active/inactive detect output the logic for the s cdt pin is [analog interface hsync detection] or [digital interface de detection]. so, the s cdt pin will switch to logic low under two conditions, when neither interface is active or when the chip is in full chip power-down mode. the data outputs are automatically three-stated when s cdt is low. this pin can be read by a controller in order to determine periods of inactivity. scan function scan in data input for scan function data can be loaded serially into the 48-bit scan register through this pin, clocking it in with the scan clk pin. it then comes out of the 48 data outputs in parallel. this function is useful for loading known data into a graphics controller chip for testing purposes. scan out data output for scan function the data in the 48-bit scan register can be read through this pin. data is read on a fifo basis and is clocked via the scan clk pin. scan clk data clock for scan function this pin clocks the data through the scan register. it controls both data input and data output.
rev. 0 AD9887A ?1 table ii. analog interface pin list pin pin pin type mnemonic function value number analog video inputs r ain analog input for converter r 0.0 v to 1.0 v 119 g ain analog input for converter g 0.0 v to 1.0 v 110 b ain analog input for converter b 0.0 v to 1.0 v 100 external hsync horizontal sync input 3.3 v cmos 82 vsync vertical sync input 3.3 v cmos 81 sync/clock sogin sync-on-green input 0.0 v to 1.0 v 108 inputs clamp clamp input (external clamp signal) 3.3 v cmos 93 coast pll coast signal input 3.3 v cmos 84 ckext external pixel clock input (to bypass internal pll) 3.3 v cmos 83 or 10 k ? to v dd ckinv adc sampling clock invert 3.3 v cmos 94 sync outputs hsout hsync output (phase-aligned with datack and datack ) 3.3 v cmos 139 vsout vsync output 3.3 v cmos 138 sogout composite sync 3.3 v cmos 140 voltage reference refout internal reference output (bypass with 0.1 f to ground) 1.25 v 126 refin reference input (1.25 v 10%) 1.25 v 10% 125 clamp voltages r midsc v voltage output equal to the red converter midscale voltage. 0.5 v 50% 120 r clamp vd uring midscale clamping, the red input is clamped to this pin. 0.0 v to 0.75 v 118 g midsc v voltage output equal to the green converter midscale voltage. 0.5 v 50% 111 g clamp v during midscale clamping, the green input is clamped to this pin. 0.0 v to 0.75 v 109 b midsc v voltage output equal to the blue converter midscale voltage. 0.5 v 50% 101 b clamp v during midscale clamping, the blue input is clamped to this pin. 0.0 v to 0.75 v 99 pll filter filt connection for external filter components for internal pll 78 power supply v d main power supply 3.3 v 5% pv d pll power supply (nominally 3.3 v) 3.3 v 5% v dd output power supply 3.3 v or 2.5 v 5% gnd ground 0 v pin function details (analog interface) inputs r ain analog input for red channel g ain analog input for green channel b ain analog input for blue channel high-impedance inputs that accept the red, green, and blue channel graphics sig nals, respectively. for rgb, the three channels are identical and can be used for any colors, but colors are assigned for convenient reference. for proper 4:2:2 formatting in a yuv appli- cation, the y channel must be connected to the g ain input, u must be connected to the b ain input, and v must be connected to the r ain input. t hey accommodate input signals ranging from 0.5 v to 1.0 v full scale. signals should be ac-coupled to these pins to support clamp operation. hsync horizontal sync input this input receives a logic signal that estab- lishes the horizontal timing reference and provides the frequency reference for pixel clock generation. the logic sense of this pin is controlled by serial register 0fh bit 7 ( hsync polarity). only the leading edge of hsync is active, the t railing edge is ignored. when hsync polarity = 0, the falling edge of hsync is used. when hsync polarity = 1, the rising edge is active. the input includes a schmitt trigger for noise immunity, with a nominal input threshold of 1.5 v. e lectrostatic discharge (esd) protection diodes will conduct heavily if this pin is driven more than 0.5 v above the maximum toler- ance voltage (3.3 v), or more than 0.5 v below ground. vsync vertical sync input this is the input for vertical sync. sogin sync-on-green input this input is provided to assist with processing signals with embedded sync, typically on the green channel. the pin is connected to a high-speed comparator with an internally generated threshold, which is set to 0.15 v above the negative peak of the input signal. when connected to an ac-coupled graphics signal with embedded sync, it will produce a noninverting digital output on sogout. w hen not used, this input should be left unconnected. for more details on this func- tion and how it should be con ? gured, refer to the sync-on-green section.
rev. 0 ?2 AD9887A clamp external clamp input (optional) this logic input may be used to de ? ne the time during which the input signal is clamped to the reference dc level (ground for rgb or midscale for yuv). it should be exercised when the reference dc level is known to be present on the analog input channels, typically during the back porch of the graphics signal. the clamp pin is enabled by setting con- trol bit extclmp to 1, (the default power-up is 0). when disabled, this pin is ignored and the clamp timing is determined internally by counting a delay and duration from the trailing edge of the hsync input. the logic sense of this pin is controlled by clampol. when not used, this pin must be grounded and extclmp programmed to 0. coast clock generator coast input (optional) this input may be used to cause the pixel clock generator to stop synchronizing with hsync and continue producing a clock at its current frequency and phase. this is useful when processing signals from sources that fail to produce horizontal sync pulses when in the vertical interval. the coast signal is generally not required for pc-generated signals. appli- cations requiring coast can do so through the internal coast found in the sync processing engine. the logic sense of this pin is controlled by coast polarity. when not used, this pin may be grounded and coast polarity programmed to 1, or tied high and coast polarity programmed to 0. coast polarity defaults to 1 at power-up. ckext external clock input (optional) this pin may be used to provide an external clock to the AD9887A, in place of the clock internally generated from hsync. it is enabled by programming extclk to 1. when an external clock is used, all other inter- nal functions operate normally. when unused, this pin should be tied to v dd or to ground, and extclk programmed to 0. the clock phase adjustment still operates when an external clock source is used. ckinv sampling clock inversion (optional) t his pin may be used to invert the pixel sampling clock, which has the effect of shifting the sampling phase 180 . this is in support of a lternate pixel sampling mode, wherein h igher frequency input signals (up to 340 mpps) may be captured by ? rst sam- pling the odd pixels, then capturing the even pixels on the subsequent frame. t his pin should be exercised only during blank- ing intervals (typically vertical blanking) as it may produce several samples of corrupted data dur ing the phase shift. ckinv should be grounded when not used. either or both signals may be used, depending on the timing mode and interface design employed. hsout horizontal sync output a reconstructed and phase-aligned version of the hsync input. both the polarity and dura tion of this output can be programmed via serial bus registers. by maintaining alignment with datack, d atack , and data, data timing with respect to horizontal sync can always be determined. sogout sync-on-green slicer output this pin can be programmed to output either the output from the sync-on-green slicer comparator or an unprocessed but delayed version of the hsync input. see the sync block diagram to view how this pin is connected. the output from this pin is the composite sync without additional processing from the AD9887A. refout internal reference output output from the internal 1.25 v band gap refer- ence. this output is intended to drive relatively light loads. it can drive the AD9887A refer ence i nput directly but should be externally buff ered if it is used to drive other loads as well. the absolute accuracy of this output is 4%, and the temperature coef ? cient is 50 ppm, w hich is adequate for most AD9887A appli- cations. if higher accuracy is required, an external reference may be employed instead. if an external reference is used, connect this pin to ground through a 0.1 f capacitor. refin reference input the reference input accepts the master refer- ence voltage for all AD9887A internal circuitry (1.25 v 10%). it may be driven directly by the refout pin. its high impedance presents a very light load to the reference source. this pin should always be bypassed to ground with a 0.1 f capacitor. filt external filter connection for proper operation, the pixel clock generator pll requires an external ? lter. connect the ? lter shown in figure 7 to this pin. for optimal performance, minimize noise and parasitics on this node.
rev. 0 AD9887A ?3 outputs red a data output, red channel, port a/even red b data output, red channel, port b/odd green a data output, green channel, port a/even green b data output, green channel, port b/odd blue a data output, blue channel, port a/even blue b data output, blue channel, port b/odd these are the main data outputs. bit 7 is the msb. each channel has two ports. when the part is operated in single-channel mode (demux = 0), all data are presented to port a, and port b is placed in a high impedance state. programming demux to 1 established dual- channel mode, wherein alternate pixels are presented to port a and port b of each channel. these will appear simultaneously, two pixels presented at the time of every second input pixel, when par is set to 1 (parallel mode). when par = 0, pixel data appear alternately on the two ports, one new sample with each incoming pixel (interleaved mode). in dual-channel mode, the ? rst pixel after hsync is routed to port a. the second pixel goes to port b, the third to a, etc. the delay from pixel sampling time to output is ? xed. when the sampling time is changed by adjusting the phase register, the output timing is shifted as well. the datack, datack , and hsout outputs are also moved, so the timing relationship among the signals is maintained. datack data output clock datack data output clock complement differential data clock output signals to be used to strobe the output data and hsout into external logic. they are produced by the internal clock gen- erator and are synchronous with the internal pixel sampling clock. when the AD9887A is operated in single- channel mode, the output frequency is equal to the pixel sampling frequency. when operating in dual-channel mode, the clock frequency is one-half the pixel frequency. when the sampling time is changed by adjusting the phase register, the output timing is shifted as well. the data, datack, datack, and hsout outputs are all moved, so the timing relationship among the signals is maintained. power supply v d main power supply these pins supply power to the main elements of the circuit. it should be ? ltered to be as quiet as possible. v dd digital output power supply these supply pins are identi ? ed separately from the v d pins so special care can be taken to minimize output noise transferred into the sensitive analog circuitry. if the AD9887A is interfacing with lower- voltage logic, v dd may be connected to a lower supply voltage (as low as 2.2 v) for compatibility. pv d clock generator power supply the most sensitive portion of the AD9887A is the clock generation circuitry. these pins provide power to the clock pll and help the user design for optimal performance. the designer should provide noise-free power to these pins. gnd ground the ground return for all circuitry on-chip. it is recommended that the application circuit board have a single, solid ground plane. theory of operation (interface detection) active interface detection and selection the AD9887A includes circuitry to detect whether an interface is active (see table iii). for detecting the analog interface, the circuitry monitors the presence of hsync, vsync, and sync-on-green. the result of the detection circuitry can be read from the 2-wire serial inter face bus at address 11h bits 7, 6, and 5, respectively. if one of these sync signals disappears, the maximum time it takes for the cir cuitry to detect it is 100 ms. there are two stages for detecting the digital interface. the ? rst stage searches for the presence of the digital interface clock. the circuitry for detecting the digital interface clock is active even when the digital interface is powered down. the result of this detection stage can be read from the 2-wire serial interface bus at address 11h bit 4. if the clock disappears, the maximum time it takes for the circuitry to detect it is 100 ms. once a digital inter- face clock is detected, the digital interface is powered up and the second stage of detection begins. during the second stage, the circuitry searches for 32 consecutive des. once 32 des are found, the detection process is complete. there is an override for the automatic interface selection. it is the aio bit (active interface override). when the aio bit is set to logic 0, the automatic circuitry will be used. when the aio bit is set to logic 1, the ais bit will be used to determine the active interface rather than the automatic circuitry.
rev. 0 ?4 AD9887A power management t he AD9887A is a dual interface device with shared outputs. only one interface can be used at a time. for this reason, the chip automatically powers down the unused interface. when the analog interface is being used, most of the digital interface circuitry is powered down and vice versa. this helps to mini mize the AD9887A total power dissipation. in addition, if neither interface has activity on it, the chip powers down both interfaces. the AD9887A uses the activity detect circuits, the active inter face bits in the serial registers, the active interface override bits, and the power-down bit to determine the correct power state. in a given power mode not all circuitry in the inactive interface is powered down completely. when the digital interface is active, the band gap reference and hsync detect circuitry is not powered down. when the analog interface is active, the digital interface clock detect circuit is not powered down. table iv summarizes how the AD9887A determines which power mode to be in and what circuitry is powered on/off in each of these modes. the power- down command has priority, followed by the active interface override, and then the automatic circuitry. table iii. interface selection controls analog digital active aio interface detect interface detect ais interface description 1 xx0 analog force the analog interface active. 1d igital force the digital interface active. 0 00x none neither interface was detected. both interfaces are powered down and the syncdt pin gets set to logic 0. 01x di g ita l the digital interface was detected. power down the analog interface. 10x analog the analog interface was detected. power down the digital interface. 10x analog both interfaces were detected. the analog interface has priority. 1d ig ita l both interfaces were detected. the digital interface has priority. table iv. power-down mode descriptions inputs analog digital active active power- interface interface interface interface mode down 1 detect 2 detect 3 override select powered on or comments soft power-down (seek mode) 1 0 0 0 x serial bus, digital interface clock detect, analog interface activity detect, sog, band gap reference digital interface on 1 0 1 0 x serial bus, digital interface, analog in terface activity detect, sog, outputs, band gap reference analog interface on 1 1 0 0 x serial bus, analog interface, digital inter face clock detect, sog, outputs, band gap reference serial bus arbitrated interface 1 1 1 0 0 same as analog interface on mode serial bus arbitrated interface 1 1 1 0 1 same as digital interface on mode override to analog interface 1 x x 1 0 same as analog interface on mode override to digital interface 1 x x 1 1 same as digital interface on mode absolute power-down 0 x x x x serial bus notes 1 power-down is controlled via bit 0 in serial bus register 12h. 2 analog interface detect is determined by or-ing bits 7, 6, and 5 in serial bus register 11h. 3 digital interface detect is determined by bit 4 in serial bus register 11h.
rev. 0 AD9887A ?5 theory of operation and design guide (analog interface) general description the AD9887A is a fully integrated solution for capturing analog rgb signals and digitizing them for display on flat panel monitors or projectors. the device is ideal for implementing a computer in ter face in hdtv monitors or as the fr ont end to high perfor- man ce video scan converters. implemented in a high performance cmos process, the inter face can capture signals with pixel rates of up to 170 mhz and, with an alternate pixel sampling mode, up to 340 mhz. the AD9887A includes all necessary input buffering, signal dc r estoration (clamping), offset and gain (brightness and contrast) adjustment, pixel clock generation, sampling phase control, and output data formatting. all controls are programmable via a 2-wire serial interface. full integration of these sensitive analog functions makes system design straightforward and less sensitive to the physical and electrical environment. with an o perating temperature range of 0 c to 70 c, the device re quires no special environmental considerations. input signal handling the AD9887A has three high impedance analog input pins for the red, green, and blue channels. they will accommodate signals ranging from 0.5 v to 1.0 v p-p. signals are typically brought onto the interface board via a dvi-i connector, a 15-lead d connector, or bnc connectors. the AD9887A should be located as close as practical to the input connector. signals should be routed via matched-impedance traces (normally 75 ? ) to the ic input pins. at that point the signal should be resistively terminated (75 ? to the signal ground return) and capacitively coupled to the ad 9887a inputs through 47 nf capacitors. these capacitors form part of the dc restoration circuit (see figure 1). in an ideal world of perfectly matched impedances, the best per for- mance can be obtained with the widest possible signal bandwidth. the wide bandwidth inputs of the AD9887A (330 mhz) can track the input signal continuously as it moves from one pixel level to the next and digitize the pixel during a long, flat pixel time. in many systems, however, there are mismatches, reflec tions, and noise that can result in excessive ringing and distortion of the input waveform. this makes it more dif ? cult to establish a sampling phase that provides good image quality. it has been shown that a small inductor in series with the input is effective in rolling off the input bandwidth slightly and providing a high quality signal over a wider range of conditions. using a fair-rite #2508051217z0 high-speed signal chip bead inductor in the circuit of figure 1 gives good results in most applications. rgb input r ain g ain b ain 47nf 75 figure 1. analog input interface circuit hsync, vsync inputs the AD9887A receives a horizontal sync signal and uses it to generate the pixel clock and clamp timing. it is possible to operate the AD9887A without applying hsync (using an external clock, external clamp) but a number of features of the chip will be unavailable, so it is recommended that hsync be provided. this can be either a sync signal directly from the graphics source, or a preprocessed ttl or cmos level signal. the hsync input includes a schmitt trigger buffer and is capable of handling signals with long rise times, with superior noise immunity. in typical pc-based graphic systems, the sync signals are simply ttl-level drivers feeding unshielded wires in the monitor cable. as such, no termination is required or desired. when the vsync input is selected as the source for vsync, it is used for coast generation and is passed through to the vsout pin. serial control port t he s erial control port is designed for 3.3 v l ogic. if there are 5 v drivers on the bus, these pins should be protected with 150 ? series resistors placed between the pull-up resistors and the input pins. output signal handling the digital outputs are designed and speci ? ed to operate from a 3.3 v power supply (v dd ). they can also work with a v dd as low as 2.5 v for compatibility with other 2.5 v logic. clamping rgb clamping to digitize the incoming signal properly, the dc offset of the input must be adjusted to ? t the range of the on-board a/d converters. most graphics systems produce rgb signals with black at ground and white at approximately 0.75 v. however, if sync signals are embedded in the graphics, the sync tip is often at ground and black is at 300 mv. the white level will be approximately 1.0 v. some common rgb line ampli ? er boxes use emitter-follower buffers to split signals and increase drive capability. this intro- duces a 700 mv dc offset to the signal, which is removed by clamping for proper capture by the AD9887A. the key to clamping is to identify a portion (time) of the signal when the graphic system is known to be producing black. originating from crt displays, the electron beam is blanked by sending a black level during horizontal retrace to prevent disturbing the image. most graphics systems maintain this format of sending a black level between active video lines. an offset is then introduced which results in the a/d converters producing a black output (code 00h) when the known black input is present. the offset then remains in place when other signal levels are processed, and the entire signal is shifted to eliminate offset errors. in systems with embedded sync, a blacker-than-black signal (hsync) is produced briefly to signal the crt that it is time to begin a retrace. for obvious reasons, it is important to avoid clamping on the tip of hsync. fortunately, there is virtually always a period following hsync called the back porch where a good black reference is provided. this is the time when clamping should be done. the clamp timing can be established by exercising the clamp pin at the appropriate time (with extclmp = 1). the polarity of this signal is set by the clamp polarity bit.
rev. 0 ?6 AD9887A an easier method of clamp timing employs the AD9887A internal clamp timing generator. the clamp placement register is pro- grammed with the number of pixel clocks that should pass after the trailing edge of hsync before clamping starts. a second register (clamp duration) sets the duration of the clamp. these are both 8-bit values, providing considerable flexibility in clamp generation. the clamp timing is referenced to the trailing edge of hsync, the back porch (black reference) always follows hsync. a good starting point for establishing clamping is to set the clamp placement to 08h (providing eight pixel periods for the graphics signal to stabilize after sync) and set the clamp duration to 14h (giving the clamp 20 pixel periods to re-establish the black reference). the value of the external input coupling capacitor affects the performance of the clamp. if the value is too small, there can be an amplitude change during a horizontal line time (between clamping intervals). if the capacitor is too large, it will take exces- sively long for the clamp to recover from a large change in incoming signal offset. the recommended value (47 nf) results in recovery from a step error of 100 mv to within 1/2 lsb in 10 lines using a clamp duration of 20 pixel periods on a 60 hz sxga signal. yuv clamping yuv signals are slightly different from rgb signals in that the dc reference level (black level in rgb signals) will be at the midpoint of the u and v video signal. for these signals, it can be necessary to clamp to the midscale range of the a/d converter range (80h) rather than bottom of the a/d converter range (00h). clamping to midscale rather than ground can be accomplished by setting the clamp select bits in the serial bus register. each of the three converters has its own selection bit so that they can be clamped to either midscale or ground independently. these bits are located in register 0fh and are bits 0 C 2. the midscale reference voltage that each a/d converter clamps to is provided independently on the r midsc v, g midsc v, and b midsc v pins. each converter must have its own midscale refer- ence because both offset adjustment and gain adjustment for each converter will affect the dc level of midscale. during clamping, the y and v converters are clamped to their respective midscale reference input. these inputs are pins b clamp v and r clamp v for the u and v converters, respectively. the typical connections for both rgb and yuv clamping are shown below in figure 2. note: if midscale clamping is not required, all of the midscale voltage outputs should still be connected to ground through a 0.1 f capacitor. r midsc v r clamp v g midsc v g clamp v b midsc v b clamp v 0.1 f 0.1 f 0.1 f figure 2. typical clamp con?uration for rbg/yuv applications gain and offset control the AD9887A can accommodate input signals with inputs ranging from 0.5 v to 1.0 v full scale. the full-scale range is set in three 8-bit registers (red gain, green gain, and blue gain). a code of 0 establishes a minimum input range of 0.5 v; 255 c orresponds with the maximum range of 1.0 v. note that in creasing the gain setting results in an image with less contrast. the offset control shifts the entire input range, resulting in a change in image brightness. three 7-bit registers (red offset, green offset, blue offset) provide independent settings for each channel. the offset controls provide a 63 lsb adjustment range. this range is connected with the full-scale range, so if the input range is doubled (from 0.5 v to 1.0 v) then the offset step size is also doubled (from 2 mv per step to 4 mv per step). figure 3 illustrates the interaction of gain and offset controls. the magnitude of an lsb in offset adjustment is proportional to t he full-scale range, so changing the full-scale range also changes the offset. the change is minimal if the offset setting is near midscale. when changing the offset, the full-scale range is not affected, but the full-scale level is shifted by the same am ount as the zero-scale level. gain 1.0 0.0 00h ffh input range (v) 0.5 offset = 00h offset = 3fh offset = 7fh offset = 00h offset = 7fh offset = 3fh figure 3. gain and offset control sync-on-green the sync-on-green input operates in two steps. first, it sets a baseline clamp level from the incoming video signal with a negative peak detector. second, it sets the sync trigger level (nominally 150 mv above the negative peak). the exact trigger level is variable and can be programmed via register 11h. the sync-on-green input must be ac-coupled to the green analog input through its own capacitor as shown in figure 4. the value of the capacitor must be 1 nf 20%. if sync-on-green is not used, this connection is not required and sogin should be left unconnected. (note: the sync-on-green signal is always negative polarity.) please refer to the sync processing section for more information. g ain sogin 47nf 1nf r ain 47nf b ain 47nf figure 4. typical clamp con?uration for rgb/yuv applications
rev. 0 AD9887A ?7 clock generation a phase locked loop (pll) is employed to generate the pixel clock. the hsync input provides a reference frequency for the pll. a voltage controlled oscillator (vco) generates a much higher pixel clock frequency. this pixel clock is divided by the pll divide value (registers 01h and 02h) and phase compared with the hsync input. any error is used to shift the vco frequency and maintain lock between the two signals. the stability of this clock is a very important element in provid- ing the clearest and most stable image. during each pixel time, there is a period when the signal is slewing from the old pixel amplitude and settling at its new value. then there is a time when the input voltage is stable, before the signal must slew to a new value (see figure 5). the ratio of the slewing time to the stable time is a function of the bandwidth of the graphics dac and the bandwidth of the transmission system (cable and t ermi- nation). it is also a function of the overall pixel rate. clearly, if the dynamic characteristics of the system remain ? xed, the slewing and settling times are likewise ? xed. this time must be sub- tracted from the total pixel period, leaving the stable period. at higher pixel frequencies, the total cycle time is shorter, and the stable pixel time becomes shorter as well. pixel clock invalid sample times figure 5. pixel sampling times pixel clock ( mhz ) 6 5 0 jitter (%) 4 3 2 1 176.0 25.1 31.5 36.0 40.0 50.0 56.2 65.0 75.0 78.7 85.5 94.5 108.0 135.0 158.0 162.0 figure 6. pixel clock jitter vs. frequency any jitter in the clock reduces the precision with which the sampling time can be determined, and must also be subtracted from the stable pixel time. considerable care has been taken in the design of the AD9887A s clock generation circuit to minimize jitter. as indicated in fi g ure 6, the clock jitter of the AD9887A is less than 6% of the total pixel time in all operating modes, making the reduction in the valid sampling time due to jitter negligible. the pll characteristics are determined by the loop ? lter design, by the pll charge pump current, and by the vco range setting. the loop ? lter design is illustrated in figure 7. recommended settings of vco range and charge pump current for vesa standard display modes are listed in table vii. c p 0.0039 f c z 0.039 f r z 3.3k filt pv d figure 7. pll loop filter detail four programmable registers are provided to optimize the perfor- mance of the pll. these registers are: 1. the 12-bit divisor register. the input hsync frequencies range from 15 khz to 110 khz. the pll multiplies the frequency of the hsync signal, producing pixel clock frequencies in the range of 12 mhz to 170 mhz. the divisor register controls the exact multiplication factor. this register may be set to any value between 221 and 4095. (the divide ratio that is actually used is the programmed divide ratio plus one.) 2. the 2-bit vco range register. to lower the sensitivity of the output frequency to noise on the control signal, the vco operat- ing frequency range is divided into four overlapping regions. the vco range register sets this operating range. because there are only three possible regions, only the two least-signi ? cant bits of the vco range register are used. the frequency ranges for the lowest and highest regions are shown in table v. table v. vco frequency ranges pixel clock pv1 pv0 range (mhz) 00 12 C 37 01 37 C 74 10 74 C 140 11 140 C 170 3. the 3-bit charge pump current register. this register allows the current that drives the low pass loop ? lter to be varied. the possible current values are listed in table vi. table vi. charge pump current/control bits ip2 ip1 ip0 current ( a) 00050 001 100 010 150 011 250 100 350 101 500 110 750 11 1 1500
rev. 0 ?8 AD9887A 4. the 5-bit phase adjust register. the phase of the generated sampling clock may be shifted to locate an optimum sampling point within a clock cycle. the phase adjust register pro vides 32 phase-shift steps of 11.25 each. the hsync signal with an identical phase shift is available through the hsout pin. phase adjustment is still available if the pixel clock is being provided externally. table vii. recommended vco range and charge pump current settings for standard display formats horizontal refresh frequency pixel rate standard resolution rate (hz) (khz) (mhz) vcornge current vga 640 480 60 31.5 25.175 00 011 72 37.7 31.500 00 100 75 37.5 31.500 00 100 85 43.3 36.000 00 101 svga 800 600 56 35.1 36.000 00 101 60 37.9 40.000 01 011 72 48.1 50.000 01 011 75 46.9 49.500 01 011 85 53.7 56.250 01 100 xga 1024 768 60 48.4 65.000 01 101 70 56.5 75.000 10 011 75 60.0 78.750 10 011 80 64.0 85.500 10 011 85 68.3 94.500 10 100 sxga 1280 1024 60 64.0 108.000 10 100 75 80.0 135.000 10 101 85 91.1 157.500 11 101 uxga 1600 1200 60 75.0 162.000 10 101 the coast allows the pll to continue to run at the same frequency, in the absence of the incoming hsync signal. this may be used during the vertical sync period, or any other time that the hsync signal is unavailable. the polarity of the coast signal may be set through the coast polarity bit. also, the polarity of the hsync signal may be set through the hsync polarity bit. if not using automatic polarity detec tion, the hsync and coast polarity bits should be set to match the polarity of their respective signals. adc dac dac 7 8 offset gain ref x1.2 in clamp v off 8 figure 8. adc block diagram (single-channel output) 1v input range v off (128 codes) input range 0.5v v off (128 codes) offset range 0v 0v offset range figure 9. relationship of offset range to input range
rev. 0 AD9887A ?9 scan function the scan function is intended as a pseudo jtag function for manufacturing test of the board. the ordinary operation of the AD9887A is disabled during scan. to enable the scan function, set register 14h, bit 2 to 1. to scan in data to all 48 digital outputs, apply 48 serial bits of data and 48 clocks (typically 5 mhz, max of 20 mhz) to the scan in and scan clk pins, respectively. the data is shifted in on the rising edge of scan clk . the first serial bit shifted in will appear at the red a<7> output after one clock cycle. after 48 clocks, the first bit is shifted all the way to the blue b<0>. the 48th bit will now be at the red a<7> output. if scan clk continues after 48 cycles, the data will continue to be shifted from red a<7> to blue b<0> and will come out of the scan out pin as serial data on the falling edge of scan clk . this is illustrated in figure 10. a setup time (t su ) of 3 ns should be plenty and no hold time (t hold ) is required ( 0 ns). this is illustrated in figure 11. t su = 3ns t hold = 0ns scan clk scan in figure 11. scan setup and hold alternate pixel sampling mode a logic 1 input on clock invert (ckinv, pin 94) inverts the nominal adc clock. ckinv can be switched between frames to implement the alternate pixel sampling mode. this allows higher effective image resolution to be achieved at lower pixel rates but with lower frame rates. on one frame, only even pixels are digitized. on the subsequent fr ame, odd pixels are sampled. by reconstructing the entire frame in the graphics controller, a complete image can be recon- structed. this is very similar to the interlacing process that is employed in broadcast television systems, but the interlacing is vertical instead of horizontal. the frame data is still presented to the display at the full desired refresh rate (usually 60 hz) so no flicker artifacts are added. oeoeoeoeoeoe oeoeoeoeoeoe oeoeoeoeoeoe oeoeoeoeoeoe oeoeoeoeoeoe oeoeoeoeoeoe oeoeoeoeoeoe oeoeoeoeoeoe oeoeoeoeoeoe oeoeoeoeoeoe oeoeoeoeoeoe figure 12. odd and even pixels in a frame o1 o1 o1 o1 o1 o1 o1 o1 o1 o1 o1 o1 o1 o1 o1 o1 o1 o1 o1 o1 o1 o1 o1 o1 o1 o1 o1 o1 o1 o1 o1 o1 o1 o1 o1 o1 o1 o1 o1 o1 o1 o1 o1 o1 o1 o1 o1 o1 o1 o1 o1 o1 o1 o1 o1 o1 o1 o1 o1 o1 o1 o1 o1 o1 o1 o1 figure 13. odd pixels from frame 1 e2 e2 e2 e2 e2 e2 e2 e2 e2 e2 e2 e2 e2 e2 e2 e2 e2 e2 e2 e2 e2 e2 e2 e2 e2 e2 e2 e2 e2 e2 e2 e2 e2 e2 e2 e2 e2 e2 e2 e2 e2 e2 e2 e2 e2 e2 e2 e2 e2 e2 e2 e2 e2 e2 e2 e2 e2 e2 e2 e2 figure 14. even pixels from frame 2 o1e2o1e2o1e2o1e2o1e2o1e2 o1e2o1e2o1e2o1e2o1e2o1e2 o1e2o1e2o1e2o1e2o1e2o1e2 o1e2o1e2o1e2o1e2o1e2o1e2 o1e2o1e2o1e2o1e2o1e2o1e2 o1e2o1e2o1e2o1e2o1e2o1e2 o1e2o1e2o1e2o1e2o1e2o1e2 o1e2o1e2o1e2o1e2o1e2o1e2 o1e2o1e2o1e2o1e2o1e2o1e2 o1e2o1e2o1e2o1e2o1e2o1e2 o1e2o1e2o1e2o1e2o1e2o1e2 figure 15. combine frame output from graphics controller x bit 1 bit 2 x xx bit 1 bit 2 bit 47 bit 48 x bit 46 bit 47 bit 48 x scan clk red a<7> blue b<0> scan out scan in bit 1 bit 2 bit 3 bit 1 bit 2 bit 3 xxx x x x figure 10. scan timing
rev. 0 ?0 AD9887A o3e2o3e2o3e2o3e2o3e2o3e2 o3e2o3e2o3e2o3e2o3e2o3e2 o3e2o3e2o3e2o3e2o3e2o3e2 o3e2o3e2o3e2o3e2o3e2o3e2 o3e2o3e2o3e2o3e2o3e2o3e2 o3e2o3e2o3e2o3e2o3e2o3e2 o3e2o3e2o3e2o3e2o3e2o3e2 o3e2o3e2o3e2o3e2o3e2o3e2 o3e2o3e2o3e2o3e2o3e2o3e2 o3e2o3e2o3e2o3e2o3e2o3e2 o3e2o3e2o3e2o3e2o3e2o3e2 figure 16. subsequent frame from controller timing (analog interface) t he following timing diagrams show the operation of the AD9887A analog interface in all clock modes. the part estab lishes timing by having the sample that corresponds to the pixel digi tized when the leading edge of hsync occurs sent to the a data port. in dual-channel mode, the next sample is sent to the b port. future samples are alternated between the a and b data ports. in single-channel mode, data is only sent to the a data port, and the b port is placed in a high im pedance state. the output data clock signal is created so that its rising edge always occurs between a data transitions, and can be used to latch the output data externally. pxlclk any output signal datack (output) t skew t dcycle t per data out figure 17. analog output timing hsync timing ho rizontal sync is processed in the AD9887A to eliminate am biguity in the timing of the leading edge with respect to the phase-delayed pixel clock and data. the hsync input is used as a reference to generate the pixel sampling clock. the sampling phase can be adjusted, with respect to hsync, through a full 360 in 32 steps via the phase adjust regis- ter (to optimize the pixel sampling time). display systems use hsync to align memory and display write cycles, so it is impor- tant to have a stable timing relationship between hsync output (hsout) and data clock (datack). three things happen to horizontal sync in the AD9887A. first, the polarity of hsync input is determined and will thus have a known output polarity. the known output polarity can be pro- grammed either active high or active low (register 04h, bit 4). second, hsout is aligned with datack and data outputs. third, the duration of hsout (in pixel clocks) is set via register 07h. hsout is the sync signal that should be used to drive the rest of the display system. coast timing in most computer systems, the hsync signal is provided con- tinuously on a dedicated wire. in these systems, the coast input and function are unnecessary, and should not be used. in some systems, however, hsync is disturbed during the vertical sync period (vsync). in some cases, hsync pulses disappear. in other systems, such as those that employ composite sync (c sync) signals or embed sync-on-green (sog), hsync includes equaliza- tion pulses or other distortions during vsync. to avoid u psetting the clock generator during vsync, it is important to ignore these distortions. if the pixel clock pll sees extraneous pulses, it will attempt to lock to this new frequency, and will have changed frequency by the end of the vsync period. it will then take a few lines of correct hsync timing to recover at the beginning of a new frame, resulting in a tearing of the image at the top of the display. the coast input is provided to eliminate this problem. it is an asynchronous input that disables the pll input and allows the clock to free-run at its then-current frequency. the pll can free-run for several lines without signi ? cant frequency drift. coast can be provided by the graphics controller or it can be internally generated by the AD9887A sync processing engine.
rev. 0 AD9887A ?1 p0 p1 p2 p3 p4 p5 p6 p7 7-pipe delay d1 d2 d3 d4 d5 d6 rgb in hsync pxck hs adcck datack d outa hsout figure 18. single-channel mode (analog interface) d0 d2 p0 p1 p2 p3 p4 p5 p6 p7 rgb in hsync pxck hs adcck datack d outa hsout d4 7-pipe delay figure 19. single-channel mode, alternate pixel sampling (even pixels) (analog interface) 7-pipe delay d1 d3 d5 p0 p1 p2 p3 p4 p5 p6 p7 rgb in hsync pxck hs adcck datack d outa hsout d7 figure 20. single-channel mode, alternate pixel sampling (odd pixels) (analog interface)
rev. 0 ?2 AD9887A p0 p1 p2 p3 p4 p5 p6 p7 7-pipe delay d4 d0 d2 d1 d3 d5 rgb in hsync pxck hs adcck datack d outa hsout d outb figure 21. dual-channel mode, interleaved outputs (analog interface), outphase = 0 p0 p1 p2 p3 p4 p5 p6 p7 8-pipe delay d0 d2 d4 rgb in hsync pxck hs adcck datack d outa hsout d outb d1 d3 d5 figure 22. dual-channel mode, parallel outputs (analog interface), outphase = 0 7-pipe delay p0 p1 p2 p3 p4 p5 p6 p7 d4 d2 d6 rgb in hsync pxck hs adcck datack d outa hsout d outb d0 figure 23. dual-channel mode, interleaved outputs, alternate pixel sampling (even pixels) (analog interface), outphase = 0
rev. 0 AD9887A ?3 8-pipe delay d1 d5 d3 p0 p1 p2 p3 p4 p5 p6 p7 rgb in hsync pxck hs adcck datack d outa hsout d outb d7 figure 24. dual-channel mode, interleaved outputs, alternate pixel sampling (odd pixels) (analog interface), outphase = 0 pxck datack 7-pipe delay p0 p1 p2 p3 p4 p5 p6 p7 d0 d4 d2 d6 rgb in hsync hs adcck d outa d outb hsout figure 25. dual-channel mode, parallel outputs, alternate pixel sampling (even pixels) (analog interface), outphase = 0 p0 p1 p2 p3 p4 p5 p6 p7 8.5-pipe delay d1 d5 d3 d7 rgb in hsync pxck hs adcck datack d outa d outb hsout figure 26. dual-channel mode, parallel outputs, alternate pixel sampling (odd pixels) (analog interface), outphase = 0
rev. 0 ?4 AD9887A 7-pipe delay p0 p1 p2 p3 p4 p5 p6 p7 u0 v2 u4 v4 rgb in hsync pxck hs adcck datack routa hsout y0 y1 y2 y3 y4 y5 gouta v0 u2 figure 27. 4:2:2 output mode table viii. digital interface pin list pin pin pin type mnemonic function value number digital video data inputs rx0+ digital input channel 0 true 62 rx0 C digital input channel 0 complement 63 rx1+ digital input channel 1 true 59 rx1 C digital input channel 1 complement 60 rx2+ digital input channel 2 true 56 rx2 C digital input channel twos complement 57 digital video clock inputs rxc+ digital data clock true 65 rxc C digital data clock complement 66 termination control r term control pin for setting the internal 53 termination resistance outputs de data enable 3.3 v cmos 137 hsout hsync output 3.3 v cmos 139 vsout vsync output 3.3 v cmos 138 ctl0, ctl1, decoded control bit outputs 3.3 v cmos 46 C 48 ctl2 hdcp ddcscl hdcp slave serial port data clock 3.3 v cmos 73 ddcsda hdcp slave serial port data i/o 3.3 v cmos 72 mcl hdcp master serial port data clock 3.3 v cmos 49 mda hdcp master serial port data i/o 3.3 v cmos 71 power supply v d main power supply 3.3 v 5% pv d pll power supply 3.3 v 5% v dd output power supply 3.3 v or 2.5 v 5% gnd ground supply 0 v gnd ground supply 0 v
rev. 0 AD9887A ?5 digital interface pin descriptions digital video data inputs rx0+ positive differential input data (channel 0) rx0 C negative differential input data (channel 0) rx1+ positive differential input data (channel 1) rx1 C negative differential input data (channel 1) rx2+ positive differential input data (channel 2) rx2 C negative differential input data (channel 2) these six pins receive three pairs of differential, low voltage swing input pixel data from a digital graphics transmitter. digital clock inputs rxc+ positive differential input clock rxc C negative differential input clock these two pins receive the differential, low voltage swing input pixel clock from a digital graphics transmitter. termination control r term internal termination set pin this pin is used to set the termination resistance for all of the digital interface high speed inputs. to set, place a resistor of value equal to 10 the desired input termination resistance between this pin (pin 53) and ground supply. typically, the value of this resistor should be 500 ? . outputs de data enable output this pin outputs the state of data enable (de). the AD9887A decodes de from the incoming stream of data. the de signal will be high during active video and will be low while there is no active video. ddcscl hdcp slave serial port data clock for use in communicating with the hdcp enabled dvi transmitter. ddcsda hdcp slave serial port data i/o for use in communicating with the hdcp enabled dvi transmitter. mcl hdcp master serial port data clock connects the eeprom for reading the encrypted hdcp keys. mda hdcp slave serial port data i/o connects the eeprom for reading the encrypted hdcp keys. ctl digital control outputs these pins output the control signals for the red and green channels. ctl0 and ctl1 correspond to the red channel s input, while ctl2 and ctl3 correspond to the green channel s input. power supply v d main power supply it should be as quiet and as ? ltered as possible. pv d pll power supply it should be as quiet and as ? ltered as possible. v dd outputs power supply the power for the data and clock outputs. it can run at 3.3 v or 2.5 v. theory of operation (digital interface) capturing of the encoded data the ? rst step in recovering the encoded data is to capture the raw data. to accomplish this, the AD9887A employs a high speed phase-locked loop (pll) to generate clocks capable of oversampling the data at the correct frequencies. the data cap- ture circuitry continuously monitors the incoming data during horizontal and vertical blanking times (when de is low) and independently selects the best sampling phase for each data channel. the phase information is stored and used until the next blanking period (one video line). data frames the digital interface data is captured in groups of 10 bits each, called a data frame. during the active data period, each frame is made up of the nine encoded video data bits and one dc balanc- ing bit. the data capture block receives this data serially but out puts each frame in parallel 10-bit words. special characters during periods of horizontal or vertical blanking time (when de is low), the digital transmitter will transmit special characters. the AD9887A will receive these characters and use them to set the video frame boundaries and the phase recovery loop for each channel. there are four s pecial characters that can be received. they are used to identify the top, bottom, left side, and right side of each video frame. the data receiver can differentiate these special characters from active data because the special characters have a different number of transitions per data frame. channel resynchronization the purpose of the channel resynchronization block is to resyn- chronize the three data channels to a single internal data clock. coming into this block, all three data channels can be on different phases of the three times oversampling pll clock (0 , 120 , and 240 ). this block can resynchronize the channels from a worst- case skew of one full input period (8.93 ns at 170 mhz). data decoder the data decoder receives frames of data and sync signals from the data capture block (in 10-bit parallel words) and decodes them into groups of eight rgb/yuv bits, two control bits, and a data enable bit (de).
rev. 0 ?6 AD9887A hdcp the AD9887A contains all the circuitry necessary for decryption of a high bandwidth digital content protection encoded dvi video stream. a typical hdcp implementation is shown in figure 28. several features of the AD9887A make this possible and add functionality to ease the implementation of hdcp. the basic components of hdcp are included in the AD9887A. a slave serial bus connects to the ddc clock and ddc data pins on the dvi connector to allow the hdcp enabled dvi trans- mitter to coordinate the hdcp algorithm with the AD9887A. a second serial port (mda/mcl) allows the AD9887A to read the hdcp keys and key selection vector (ksv) stored in an external serial eeprom. when transmitting encrypted video, the dvi transmitter enables hdcp through the ddc port. the AD9887A then decodes the dvi stream using information provided by the transmitter, hdcp keys, and ksv. the AD9887A allows the mda and mcl pins to be three-stated using the mda/mcl three-state bit (register 1b, bit 7) in the configuration registers. the three-state feature allows the eeprom to be programmed in-circuit. the mda/mcl port must be t hree-stated before attempting to program the eeprom using an external master. the keys will be stored in an i 2 c ? compatible 3.3 v serial eeprom of at least 512 bytes in size. the eeprom should have a device address of a0h. proprietary software licensed from analog devices encrypts the keys and creates properly formatted eeprom images for use in a production environment. encrypting the keys helps maintain the confidentiality of the hdcp keys as required by the hdcp v1.0 specification. the AD9887A includes hardware for decrypting the keys in the external eeprom. adi will provide a royalty free license for the proprietary software needed by customers to encrypt the keys between the AD9887A and the eeprom only after customers provide evidence of a completed hdcp adopter s license agreement and sign adi s software license agreement. the adopter s license agreement is maintained by digital content protection, llc, and can be downloaded from www.digital-cp.com. to obtain adi s software license agreement, contact the display electronics product line directly by sending an email to flatpanel_apps@analog.com. ddc clock ddc data dvi connector scl sda eeprom 3.3v 5k pull-up resistors 3.3v 5k pull-up resistors 150 series resistors ddcscl ddcsda AD9887A mcl mda 3.3v s d figure 28. hdcp implementation using the AD9887A purchase of licensed i 2 c components of analog devices or one of its sublicensed associated companies conveys a license for the purchaser under the phi lips i 2 c patent rights to use these components in an i 2 c system, provided that the system conforms to the to the i 2 c standard specification as defined by philips.
rev. 0 AD9887A ?7 general timing diagrams (digital interface) 80% 80% 20% 20% d lht d lht figure 29. digital output rise and fall time t cih , r cih t cip , r cip t cil , r cil figure 30. clock cycle/high/low times v diff = 0v t ccs v diff = 0v rx0 rx1 rx2 figure 31. channel-to-channel skew timing datack (internal) datack (pin) t skew data out figure 32. dvi output timing timing mode diagrams (digital interface) first pixel second pixel third pixel fourth pixel internal odclk datack de qe[23:0] qo[23:0] t st figure 33. 1 pixel per clock (datack inverted) first pixel second pixel third pixel fourth pixel datack de qe[23:0] qo[23:0] internal odclk t st figure 34. 1 pixels per clock (datack not inverted) first pixel second pixel third pixel fourth pixel datack de qe[23:0] qo[23:0] internal odclk t st figure 35. 2 pixels per clock first pixel second pixel third pixel fourth pixel datack de qe[23:0] qo[23:0] internal odclk t st figure 36. 2 pixels per clock (datack inverted)
rev. 0 ?8 AD9887A 2-wire serial register map the AD9887A is initialized and controlled by a set of registers, which determine the operating m odes. an external controller is employed to write and read the control registers through the 2-line serial interface port. table ix. control register map read and hex write or default register address read only bits value name function 00h ro 7:0 chip revision bits 7 through 4 represent functional revisions to the analog interface. bits 3 through 0 represent nonfunctional related revisions. revision 0 = 0000 0000. 01h r/w 7:0 01101001 pll div msb this register is for bits [11:4] of the pll divider. larger values mean the pll operates at a faster rate. this register should be loaded ? rst whenever a change is needed. (this will give the pll more time to lock.) see note 1. 02h r/w 7:4 1101 **** pll div lsb bits [7:4] lsbs of the pll divider word. links to the pll div msb to make a 12-bit register. see note 1. 03h r/w 7:2 1 ******* vco/cpmp bit 7 must be set to 1 for proper device operation. * 01 ***** bits [6:5] vco range. selects vco frequency range. (see pll description.) *** 001 ** bits [4:2] charge pump current. varies the current that drives the low-pass ? lter. (see pll description.) 04h r/w 7:3 10000 *** phase adjust adc clock phase adjustment. larger values mean more delay. (1 lsb = t/32) 05h r/w 7:0 10000000 clamp places the clamp signal an integer number of clock periods after placement the trail ing edge of the hsync signal. 06h r/w 7:0 10000000 clamp number of clock periods that the clamp signal is actively clamping. duration 07h r/w 7:0 00100000 hsync output sets the number of pixel clocks that hsout will remain active. pulsewidth 08h r/w 7:0 10000000 red gain controls adc input range (contrast) of each respective channel. bigger values give less contrast. 09h r/w 7:0 10000000 green gain 0ah r/w 7:0 10000000 blue gain 0bh r/w 7:1 1000000 * red offset controls dc offset (brightness) of each respective channel. bigger values decrease brightness. 0ch r/w 7:1 1000000 * green offset 0dh r/w 7:1 1000000 * blue offset 0eh r/w 7:3 1 ******* mode bit 7 channel mode. determines single channel or dual channel control 1 output mode. (logic 0 = single channel mode, logic 1 = dual channel mode.) * 1 ****** bit 6 output mode. determine interleaved or parallel output mode. (logic 0 = interleaved mode, logic 1 = parallel mode.) ** 0 ***** bit 5 outphase. determines which port outputs the ? rst data byte after hsync. (logic 0 = b port, logic 1 = a port.) *** 0 **** bit 4 hsync output polarity. (logic 0 = logic high sync, logic 1 = logic low sync.) **** 0 *** bit 3 vsync output invert. (logic 0 = invert, logic 1 = no invert.)
rev. 0 AD9887A ?9 table ix. control register map (continued) read and hex write or default register address read only bits value name function 0fh r/w 7:0 1 ******* p ll and bit 7 hsync polarity. indicates the polarity of incoming hsync clamp control signal to the pll. (logic 0 = active low, logic 1 = active high.) * 1 ****** bit 6 coast polarity. changes polarity of external coast signal. (logic 0 = active low, logic 1 = active high.) ** 0 ***** bit 5 clamp function. chooses between hsync for clamp signal or another external signal to be used for clamping. (logic 0 = hsync, logic 1 = clamp.) *** 1 **** bit 4 clamp polarity. valid only with external clamp signal. (logic 0 = active low, logic 1 selects active high.) **** 0 *** bit 3 extclk. shuts down the pll and allows the use of an external clock to drive the part. (logic 0 = use internal pll, logic 1 = bypassing of the internal pll.) ***** 0 ** bit 2 red clamp select logic 0 selects clamp to ground. logic 1 selects clamp to midscale (voltage at pin 120). ****** 0 * bit 1 green clamp select logic 0 selects clamp to ground. logic 1 selects clamp to midscale (voltage at pin 111). ******* 0 bit 0 blue clamp select logic 0 selects clamp to ground. logic 1 selects clamp to midscale (voltage at pin 101). 10h r/w 7:2 0 ******* mode bit 7 clk inv: data clock output invert. (logic 0 = not inverted, control 2 logic 1 = inverted.) (digital interface only.) * 0 ****** bit 6 pix select: selects either 1 or 2 pixels per clock mode. (logic 0 = 1 pixel/clock, logic 1 = 2 pixels/clock.) (digital interface only.) ** 11 **** bit 5, 4 output drive: selects between high, medium, and low output drive strength. (logic 11 or 10 = high, 01 = medium, and 00 = low.) **** 0 *** bit 3 p do : high impedance outputs. (logic 0 = normal, logic 1 = high impedance.) ***** 1 ** bit 2 sync detect (syncdt) polarity. this bit sets the polarity for the syncdt output pin. (logic 1 = active high, logic 0 = active low.) 11h ro 7:1 1 *** **** sync detect/ bit 7 analog interface hsync detect. it is set to logic 1 if hsync active interface is present on the analog interface; otherwise it is set to logic 0. * 1 ** **** bit 6 analog interface sync-on-green detect. it is set to logic 1 if sync is present on the green video input; otherwise it is set to 0. ** 1 * **** bit 5 analog interface vsync detect. it is set to logic 1 if vsync is present on the analog interface; otherwise it is set to logic 0. *** 1 **** bit 4 digital interface clock detect. it is set to logic 1 if the clock is present on the digital interface; otherwise it is set to logic 0. **** 1 *** bit 3 ai: active interface. this bit indicates which interface is active. (logic 0 = analog interface, logic 1 = digital interface.) **** * 1 ** bit 2 ahs: active hsync. this bit indicates which analog hsync is being used. (logic 0 = hsync input pin, logic 1 = hsync from sync-on-green.) **** ** 1 * bit 1 avs: active vsync. this bit indicates which analog vsync fro m sync separator.)
rev. 0 ?0 AD9887A table ix. control register map (continued) read and hex write or default register address read only bits value name function 12h r/w 7:0 0 ******* active bit 7 aio: active interface override. if set to logic 1, the user interface can select the active interface via bit 6. if set to logic 0, the active interface is selected via bit 3 in register 11h. * 0 ****** bit 6 ais: active interface select. logic 0 selects the analog inter- face as active. logic 1 selects the digital interface as active. note: the indicated interface will be active only if bit 7 is set to logic 1 or if both interfaces are active (bits 6 or 7 and 4 = logic 1 in register 11h.) ** 0 ***** bit 5 active hsync override. if set to logic 1, the user can select the hsync to be used via bit 4. if set to logic 0, the active interface is selected via bit 2 in register 11h. *** 0 **** bit 4 active hsync select. logic 0 selects hsync as the active sync. logic 1 selects sync-on-green as the active sync. note: the indicated hsync will be used only if bit 5 is set to logic 1 or if both syncs are active (bits 6, 7 = logic 1 in register 11h.) **** 0 *** bit 3 active vsync override. if set to logic 1, the user can select the vsync to be used via bit 2. if set to logic 0, the active interface is selected via bit 1 in register 11h. ***** 0 ** bit 2 active vsync select. logic 0 selects raw vsync as the output vsync. logic 1 selects sync separated vsync as the output vsync. note: the indicated vsync will be used only if bit 3 is set to logic 1. ****** 0 * bit 1 coast select. logic 0 selects the coast input pin to be used for the pll coast. logic 1 selects vsync to be used for the pll coast. ******* 1b it 0 pwrdn . full chip power-down, active low. (logic 0 =full chip power-down, logic 1 = normal.) 13h r/w 7:0 00100000 sync separator sync separator threshold sets the number of clocks the sync threshold separator will count to before toggling high or low. this should be set to some number greater than the maximum hsync or equalization pulsewidth. 14h r/w 7:0 *** 1 **** control bits bit 4 must be set to 1 for proper operation. **** 0 *** bit 3 must be set to 0 for proper operation. ***** 0 ** bit 2 scan enable. (logic 0 = not enabled, logic 1 = enabled.) ****** 0 * bit 1 coast polarity override. (logic 0 = polarity determined by chip, logic 1 = polarity set by bit 6 in register 0fh.) ******* 0 bit 0 hsync polarity override. (logic 0 = polarity determined by chip, logic 1 = polarity set by bit 7 in register 0fh.) 15h ro 7:5 0 *** **** polarity status bit 7 hsync input polarity status. (logic 1 = active high, logic 0 = active low.) * 0 ** **** bit 6 vsync output polarity status. (logic 0 = active high, logic 1 = active low.) ** 0 * **** bit 5 coast input polarity status. (logic 1 = active high, logic 0 = active low.) 16h r/w 7:2 10111 *** control bits 2 bits [7:3] sync-on-green slicer threshold **** * 1 ** bit 2 must be set to 0 for proper operation. 17h r/w 7:0 00000000 pre-coast sets the number of hsyncs that coast goes active prior to vsync. 18h r/w 7:0 00000000 post-coast sets the number of hsyncs that coast goes active following vsync. 19h r/w 7:0 00000000 test register must be set to default for proper operation. 1ah r/w 7:0 11111111 test register must be set to 01000001 for proper operation.
rev. 0 AD9887A ?1 read and hex write or default register address read only bits value name function 1bh r/w 7:0 00000000 test register must be set to 0001 0000 for proper operation. 1ch r/w 7:0 00000 *** test register bits [7:3] must be set to 00000 *** for proper operation. ***** 1 ** bit 2 cbcr output order. ****** 1 * bit 1 must be set to 0 for standard input sampling. ******* 1 4:2:2 control bit 0 output format mode select. logic 1 = 4:4:4 mode. logic 0 = 4:2:2 mode. 1dh ro 7:0 * _ ***** logic 1 = hdcp keys detected. 1eh r/w 7:0 11111111 must set to ffh for proper operation. 1fh r/w 7:0 10000100 must set to 84h for proper operation. 20h r/w 7:0 0 ******* hdcp a0; 0->address = 0x74. * 0 ****** ctrl3 mux; pin49 = ctrl3. ** 0 ***** analog input bandwidth control; 0 = high. *** 0 **** mda mcl tristate; 0 = tristate, 1 = hdcp mode. **** 1 *** oscillator source; 1 = internal, 0 = use clk on a0. ***** 0 ** normal operation. 21h r/w 7:0 00000000 must be set to default. 22h r/w 7:0 00000000 must be set to default. 23h r/w 7:0 00000000 should be set to 2ah for proper operation. 24h r/w 7:0 00000000 must be set to default. 25h r/w 7:0 11110000 set to default. 26h r/w 7:0 11111111 set to default. note 1 the AD9887A only updates the pll divide ratio when the lsbs are written to (register 02h). table ix. control register map (continued)
rev. 0 ?2 AD9887A 2-wire serial control register detail chip identification 00 7? chip revision bits 7 through 4 represent functional revisions to the analog interface. changes in these bits will generally indicate that software and/or hardware changes will be required for the chip to work properly. bits 3 through 0 represent nonfunc- tional related revisions and are reset to 0000 whenever the msbs are changed. changes in these bits are considered transparent to the user. pll divider control 01 7? pll divide ratio msbs t he eight most signi ? cant bits of the 12-bit pll divide ratio plldiv. (the operational divide ratio is plldiv + 1.) the pll derives a pixel clock from the incoming hsync signal. the pixel clock frequency is then divided by an integer value, such that the output is phase-locked to h sync. this plldiv value determines the number of pixel times (pixels plus horizontal blanking overhead) per line. this is typically 20% to 30% more than the number of active pixels in the display. the 12-bit value of the pll divider supports divide ratios from 221 to 4095. the higher the value loaded in this regis- ter, the higher the resulting clock frequency with respect to a ? xed hsync frequency. ve sa has established some standard timing speci ? ca tions, which will assist in determining the value for plldiv as a function of horizontal and vertical display resolution and frame rate (table vii). however, many computer systems do not conform pre cisely to the recommendations, and these numbers should be used only as a guide. the display system manufacturer should provide automatic or manual means for optimizing pl l div. an incorrectly set plldiv will usually produce one or more vertical noise bars on the display. the greater the error, the greater the number of bars produced. t he power-up default value of plldiv is 1693 (plldivm = 69h, p lldivl = dxh). the AD9887A updates the full divide ratio only when the lsbs are changed. writing to this register by itself will not trigger an update. 02 7? pll divide ratio lsbs the four least signi ? cant bits of the 12-bit pll divide ratio plldiv. the operational divide ratio is plldiv + 1. the power-up default value of plldiv is 1693 (plldivm = 69h, plldivl = dxh). the AD9887A updates the full divide ratio only when this register is written. clock generator control 03 7 test set to one 03 6? vco range select two bits that establish the operating range of the clock generator. vcornge must be set to correspond with the desired operating frequency (incoming pixel rate). the pll gives the best jitter performance at high fre quen- cies. for this reason, in order to output low pixel rates and still get good jitter performance, the pll actually operates at a higher frequency but then divides down the clock rate afterwards. table x shows the pixel rates for each vco range setting. the pll output divisor is automatically selected with the vco range setting. table x. vco ranges vcornge pixel rate range 00 12 C 37 01 37 C 74 10 74 C 140 11 140 C 170 the power-up default value is = 01. 03 4? current charge pump current three bits that establish the current driving the loop ? lter in the clock generator. table xi. charge pump currents current current ( a) 000 50 001 100 010 150 011 250 100 350 101 500 110 750 111 1500 see table vii for the recommended current settings. the power-up default value is current = 001. 04 7? clock phase adjust a 5-bit value that adjusts the sampling phase in 32 steps across one pixel time. each step represents an 11.25 shift in sampling phase. the power-up default value is 16. clamp timing 05 7? clamp placement an 8-bit register that sets the position of the internally generated clamp. when extclmp = 0, a clamp signal is generated inter- nally, at a position established by the clamp placement and for a duration set by the clamp duration. clamping is started (clamp placement) pixel periods after the trailing edge of hsync. the clamp placement may be programmed to any value between 1 and 255. a value of 0 is not supported. the clamp should be placed during a time that the input signal presents a stable black-level reference, usually the back porch period between hsync and the image. when extclmp = 1, this register is ignored.
rev. 0 AD9887A ?3 06 7? clamp duration an 8-bit register that sets the duration of the internally generated clamp. when extclmp = 0, a clamp signal is generated inter- nally, at a position established by the clamp placement and for a duration set by the clamp duration. clamping is started (clamp placement) pixel periods after the trailing edge of hsync, and continues for (clamp duration) pixel periods. the clamp duration may be programmed to any value between 1 and 255. a value of 0 is not supported. for the best results, the clamp duration should be set to include the majority of the black reference signal time that follows the hsync signal trailing edge. insuf ? cient clamp- ing time can produce brightness changes at the top of the screen, and a slow recovery from large changes in the average picture level (apl), or brightness. when extclmp = 1, this register is ignored. hsync pulsewidth 07 7? hsync output pulsewidth an 8-bit register that sets the duration of the hsync out put pulse. the leading edge of the hsync output is triggered by the internally generated, phase-adjusted pll feedback clock. the AD9887A then counts a number of pixel clocks equal to the value in this register. this triggers the trailing edge of the hsync output, which is also phase-adjusted. input gain 08 7? red channel gain adjust an 8-bit word that sets the gain of the red channel. the AD9887A can accommodate input signals with a full-scale range of between 0.5 v and 1.5 v p-p. setting r edgain to 255 corre sponds to an in put range of 1.0 v. a redgain of 0 establishes an input range of 0.5 v. note that increasing redgain results in the pic ture having less contrast (the input signal uses fewer of the available converter codes). see figure 3. 09 7? green channel gain adjust an 8-bit word that sets the gain of the green channel. see redgain (08). 0a 7? blue channel gain adjust an 8-bit word that sets the gain of the blue channel. see redgain (08). input offset 0b 7? red channel offset adjust a 7-bit offset binary word that sets the dc offset of the red channel. one lsb of offset adjustment equals approxi- mately one lsb change in the adc offset. therefore, the absolute magnitude of the offset adjustment scales as the gain of the channel is changed. a nominal setting of 63 results in the channel nominally clamping the back porch (during the clamping interval) to code 00. an offset setting of 127 results in the channel clamping to code 63 of the adc. an offset setting of 0 clamps to code C 63 (off the bottom of the range). increasing the value of red offset decreases the brightness of the channel. 0c 7? green channel offset adjust a 7-bit offset binary word that sets the dc offset of the green channel. see redofst (0b). 0d 7? blue channel offset adjust a 7-bit offset binary word that sets the dc offset of the blue channel. see redofst (0b). mode control 1 0e 7 channel mode a bit that determines whether all pixels are presented to a single port (a), or alternating pixels are demultiplexed to ports a and b. table xii. channel mode settings demux function 0a ll data goes to port a 1 alternate pixels go to port a and port b when demux = 0, port b outputs are in a high impedance state. the maximum data rate for single-port mode is 100 mhz. the timing diagrams show the effects of this option. the power-up default value is 1. 0e 6 output mode a bit that determines whether all pixels are presented to port a and port b simultaneously on every second datack rising edge or alternately on port a and port b on successive datack rising edges. table xiii. output mode settings parallel function 0d ata is interleaved 1d ata is simultaneous on every other data clock when in single-port mode (demux = 0), this bit is ignored. the timing diagrams show the effects of this option. the power-up default value is parallel = 1. 0e 5 output port phase one bit that determines whether even pixels or odd pixels go to port a. table xiv. output port phase settings outphase first pixel after hsync 1 port b 0 port a in normal operation (outphase = 0), when operating in dual-port output mode (demux = 1), the ? rst sample after the hsync leading edge is presented at port a. every subsequent odd sample appears at port a. all even samples go to port b. when outphase = 1, these ports are reversed and the ? rst sample goes to port b.
rev. 0 ?4 AD9887A when demux = 0, this bit is ignored as data always comes out of only port a. 0e 4 hsync output polarity one bit that determines the polarity of the hsync out- put and the sog output. table xv shows the effect of t his option. sync indicates the logic state of the sync pulse. table xv. hsync output polarity settings setting sync 0l ogic 1 (positive polarity) 1l ogic 0 (negative polarity) the default setting for this register is 1. (this option works on both the analog and digital interfaces.) 0e 3 vsync output invert one bit that inverts the polarity of the vsync output. table xvi shows the effect of this option. table xvi. vsync output polarity settings setting vsync output 0 invert 1n o invert the default setting for this register is 1. (this option works on both the analog and digital interfaces.) 0f 7 hsync input polarity a bit that must be set to indicate the polarity of the hsync signal that is applied to the pll hsync input. table xvii. hsync input polarity settings hspol function 0a ctive low 1a ctive high active low is the traditional negative-going hsync pulse. all timing is based on the leading edge of hsync, which is the falling edge. the rising edge has no effect. active high is inverted from the traditional hsync, with a positive-going pulse. this means that timing will be based on the leading edge of hsync, which is now the rising edge. the device will operate if this bit is set incorrectly, but the in ternally generated clamp position, as established by cl po s, will not be placed as expected, which may generate clamping errors. the power-up default value is hspol = 1. 0f 6 coast input polarity a bit to indicate the polarity of the coast signal that is applied to the pll coast input. table xviii. coast input polarity settings cstpol function 0a ctive low 1a ctive high active low means that the clock generator will ignore hsync inputs when coast is low, and continue operating at the same nominal frequency until coast goes high. active high means that the clock generator will ignore hsync inputs when coast is high, and continue operat- ing at the same nominal frequency until coast goes low. this function needs to be used along with the coast polarity override bit (register 14, bit 1). the power-up default value is cstpol = 1. 0f 5 clamp input signal source a bit that determines the source of clamp timing. table xix. clamp input signal source settings extclmp function 0 internally generated clamp 1 externally provided clamp signal a 0 enables the clamp timing circuitry controlled by clplace and cldur. the clamp position and dura tion is counted from the trailing edge of hsync. a 1 enables the external clamp input pin. the three c hannels are clamped when the clamp signal is active. the polarity of clamp is determined by the clampol bit. the power-up default value is extclmp = 0. 0f 4 clamp input signal polarity a bit that determines the polarity of the externally provided clamp signal. table xx. clamp input signal polarity settings extclmp function 0a ctive low 1a ctive high a logic 0 m eans that the circuit will clamp when clamp is high, and it will pass the signal to the adc when clamp is low. a logic 1 means that the circuit will clamp when clamp is low, and it will pass the signal to the adc when clamp is high. the power-up default value is clampol = 1. 0f 3 external clock select a bit that determines the source of the pixel clock. table xxi. external clock select settings extclk function 0 internally generated clock 1e xternally provided clock signal a logic 0 enables the internal pll that generates the pixel clock from an externally provided hsync.
rev. 0 AD9887A ?5 a logic 1 enables the external ckext input pin. in this mode, the pll divide ratio (plldiv) is ignored. the clock phase adjust (phase) is still functional. the power-up default value is extclk = 0. 0f 2 red clamp select a bit that determines whether the red channel is clamped to ground or to midscale. for rgb video, all three channels are referenced to ground. for ycbcr (or yuv), the y channel is referenced to ground, but the cbcr channels are referenced to midscale. clamping to midscale actually clamps to pin 118, r clamp v. table xxii. red clamp select settings clamp function 0c lamp to ground 1c lamp to midscale (pin 118) the default setting for this register is 0. 0f 1 green clamp select a bit that determines whether the green channel is clamped to ground or to midscale. table xxiii. green clamp select settings clamp function 0c lamp to ground 1c lamp to midscale (pin 109) the default setting for this register is 0. 0f 0 blue clamp select a bit that determines whether the blue channel is clamped to ground or to midscale. table xxiv. blue clamp select settings clamp function 0c lamp to ground 1c lamp to midscale (pin 99) the default setting for this register is 0. mode control 2 10 7 clk inv data output clock invert a control bit for the inversion of the output data clocks, (pins 134, 135). this function works only for the digital interface. when not inverted, data is output on the trail- ing edge of the data clock. see timing diagrams to see how this affects timing. table xxv. clock output invert settings clk inv function 0n ot inverted 1 inverted the default for this register is 0, not inverted. 10 6 pix select this bit selects either 1 or 2 pixels per clock mode for the digital interface. it determines whether the data comes out of a single port (even port only), at the full data rate, or out of two ports (both even and odd ports), at one-half the full data rate per port. a logic 0 selects 1 pixel per clock (even port only). a logic 1 selects 2 pixels per clock (both ports). see the digital interface timing diagrams, figures 33 to 36, for a visual representation of this function. note: this function operates exactly like the demux function on the analog interface. table xxvi. pix select settings pix select function 01 pixel per clock 12 pixels per clock the default for this register is 0, 1 pixel per clock. 10 5, 4 output drive these two bits select the drive strength for the high speed digital outputs (all data output and clock output pins). higher drive strength results in faster rise/fall times and in ge neral makes it easier to capture data. lower drive strength results in slower rise/fall times and helps to reduce emi and digitally generated power supply noise. the exact timing speci ? cations for each of these modes are speci ? ed in table vii. table xxvii. output drive strength settings bit 5 bit 4 result 11 high drive strength 10 medium drive strength 0x low drive strength the default for this register is 11, high drive strength. (this option works on both the analog and digital interfaces.) 10 3 p do ?ower-down outputs a bit that can put the outputs in a high impedance mode. this applies only to the 48 data output pins and the two data clock output pins. table xxviii. power-down output settings ckinv function 0n ormal operation 1 three-state the default for this register is 0. (this option works on both the analog and digital interfaces.) 10 2 sync detect polarity this pin controls the polarity of the sync detect output pin (pin 136). table xxix. sync detect polarity settings polarity function 0a ctivity = logic 1 output 1a ctivity = logic 0 output the default for this register is 0. (this option works on both the analog and digital interfaces.)
rev. 0 ?6 AD9887A sync detection and control 11 7 analog interface hsync detect this bit is used to indicate when activity is detected on the hsync input pin (pin 82). if hsync is held high or low, activity will not be detected. table xxx. hsync detection results detect function 0n o activity detected 1a ctivity detected figure 39 shows where this function is implemented. 11 6 analog interface sync-on-green detect this bit is used to indicate when sync activity is detected on the sync-on-green input pin (pin 108). table xxxi. sync-on-green detection results detect function 0n o activity detected 1a ctivity detected figure 39 shows where this function is implemented. warning: if no sync is present on the green video input, normal video may still trigger activity. 11 5 analog interface vsync detect this bit is used to indicate when activity is detected on the vsync input pin (pin 81). if vsync is held high or low, activity will not be detected. table xxxii. vsync detection results detect function 0n o activity detected 1a ctivity detected f igure 39 shows where this function is implemented. 11 4 digital interface clock detect this bit is used to indicate when activity is detected on the digital interface clock input. table xxxiii. digital interface clock detection results detect function 0n o activity detected 1a ctivity detected the sync processing block diagram shows where this function is implemented. 11 3 active interface this bit is used to indicate which interface should be active, analog, or digital. it checks for activity on the analog interface and for activity on the digital interface, then determines which should be active according to table xxxiv. speci ? cally, analog interface detection is determined by or-ing bits 7, 6, and 5 in this register. digital interface detection is determined by bit 4 in this register. if both interfaces are detected, the user can deter- mine which has priority via bit 6 in register 12h. the user can override this function via bit 7 in register 12h. if the override bit is set to logic 1, then this bit will be forced to whatever the state of bit 6 in register 12h is set to. table xxxiv. active interface results bits 7, 6, or 5 bit 4 (analog (digital detection) detection) override ai 000 soft power-down (seek mode) 0101 1000 110b it 6 in 12h xx1b it 6 in 12h ai = 0 means analog interface. ai = 1 means digital interface. the override bit is in register 12h, bit 7. 11 2 ahs?ctive hsync this bit is used to determine which hsync should be used for the analog interface, the hsync input or sync- on-green. it uses bits 7 and 6 in this register for inputs in determining which should be active. similar to the previous bit, if both hsync and sog are detected, the user can determine which has priority via bit 4 in register 12h. the user can override this function via bit 5 in register 12h. if the override bit is set to logic 1, this bit will be forced to whatever the state of bit 4 in register 12h is set to. table xxxv. active hsync results bit 7 bit 6 (hsync (sog detect) detect) override ahs 0 00bit 4 in 12h 0 101 1 000 1 10bit 4 in 12h xx1b it 4 in 12h ahs = 0 means use the hsync pin input for hsync. ahs = 1 means use the sog pin input for hsync. the override bit is in register 12h, bit 5. 11 1 avs?ctive vsync this bit is used to determine which vsync should be used for the analog interface; the vsync input or output from the sync separator. if both vsync and composite sog are detected, vsync will be selected. the user can override this function via bit 3 in register 12h. if the override bit is set to logic 1, this bit will be forced to what- ever the state of bit 2 in r egister 12h is set to.
rev. 0 AD9887A ?7 table xxxvi. active vsync results bit 5 (vsync detect) override avs 00 0 10 1 x1 bit 2 in 12h avs = 1 means sync separator. avs = 0 means vsync input. the override bit is in register 12h, bit 3. 12 7 aio?ctive interface override this bit is used to override the automatic interface selec- tion (bit 3 in register 11h). to override, set this bit to logic 1. when overriding, the active interface is set via bit 6 in this register. table xxxvii. active interface override settings aio result 0a utodetermines the active interface 1o verride, bit 6 determines the active interface the default for this register is 0. 12 6 ais?ctive interface select this bit is used under two conditions. it is used to select the active interface when the override bit is set (bit 7). alternately, it is used to determine the active interface when not overriding but both interfaces are detected. table xxxviii. active interface select settings ais result 0a nalog interface 1d igital interface the default for this register is 0. 12 5 active hsync override this bit is used to override the automatic hsync selection (bit 2 in register 11h). to override, set this bit to logic 1. when overriding, the active hsync is set via bit 4 in this register. table xxxix. active hsync override settings override result 0a utodetermines the active interface 1 override, bit 4 determines the active inter face the default for this register is 0. 12 4 active hsync select this bit is used under two conditions. it is used to select t he active hsync when the override bit is set (bit 5). alter- na tely, it is used to determine the active hsync when not overriding, but both hsyncs are detected. table xl. active hsync select settings select result 0h sync input 1 sync-on-green input the default for this register is 0. 12 3 active vsync override this bit is used to override the automatic vsync selec tion (bit 1 in register 11h). to override, set this bit to logic 1. when overriding, the active interface is set via bit 2 in this register. table xli. active vsync override settings override result 0a utodetermines the active vsync 1 override, bit 2 determines the active v sync the default for this register is 0. 12 2 active vsync select this bit is used to select the active vsync when the override bit is set (bit 3). table xlii. active vsync select settings select result 0v sync input 1 sync separator output the default for this register is 0. 12 1 coast select this bit is used to select the active coast source. the choices are the coast input pin or vsync. if vsync is s elected, the additional decision of using the vsync input pin or the output from the sync separator needs to be made (bits 3, 2). table xliii. coast select settings select result 0c oast input pin 1v sync (see above text) the default for this register is 0. 12 0 pwrdn this bit is used to put the chip in full power-down. this powers down both interfaces. see the section on power m anagement for details of which blocks are actually pow ered down. note, the chip will be unable to detect incoming activity while fully powered down. table xliv. power-down settings select result 0 power-down 1n ormal operation the default for this register is 1.
rev. 0 ?8 AD9887A digital control 13 7:0 sync separator threshold this register is used to set the responsiveness of the sync separator. it sets how many pixel clock pulses the sync separator must count to before toggling high or low. it works like a low-pass ? lter to ignore hsync pulses in order to extract the vsync signal. this register should be set to s ome number greater than the maximum hsync pulsewidth. the default for this register is 32. control bits 14 2 scan enable this register is used to enable the scan function. when enabled, data can be loaded into the AD9887A outputs serially with the scan function. the scan function utilizes three pins (scan in , scan out , and scan clk ). these pins are described in table i. table xlv. scan enable settings scan enable result 0 scan function disabled 1 scan function enabled the default for scan enable is 0 (disabled). 14 1 coast input polarity override this register is used to override the internal circuitry that det ermines the polarity of the coast signal going into the pll. table xlvi. coast input polarity override settings override bit result 0c oast polarity determined by chip 1c oast polarity determined by user t he default for coast polarity override is 0 (polarity determined by chip). 14 0 hsync input polarity override this register is used to override the internal circuitry that d etermines the polarity of the hsync signal going into the pll. table xlvii. hsync input polarity override settings override bit result 0h sync polarity determined by chip 1h sync polarity determined by user the default for hsync polarity override is 0 (polarity determined by chip). 15 7 hsync input polarity status this bit reports the status of the hsync input polarity detection circuit. it can be used to determine the polarity of the hsync input. the detection circuit s location is shown in the sync processing block diagram (figure 39). table xlviii. detected hsync i nput polarity status hsync polarity status result 0h sync polarity is negative. 1h sync polarity is positive. 15 6 vsync output polarity status this bit reports the status of the vsync output polarity detection circuit. it can be used to determine the polarity of the vsync input. the detection circuit s location is shown in the sync processing block diagram (figure 39). table xlix. detected vsync i nput polarity status vsync polarity status result 0v sync polarity is active low. 1v sync polarity is active high. 15 5 coast input polarity status this bit reports the status of the coast input polarity detection circuit. it can be used to determine the polar- ity of the coast input. the detection circuit s location is shown in the sync processing block diagram (figure 39). table l. detected coast input polarity status coast polarity status result 0c oast polarity is negative. 1c oast polarity is positive. 16 7? sync-on-green slicer threshold this register allows the comparator threshold of the sync-on-green slicer to be adjusted. this register adjusts the comparator threshold in steps of 10 mv. a setting of zero results in a 330 mv threshold. the setting of 31 results in a 10 mv threshold. the default setting is 23 and corresponds to a threshold value of 70 mv. 17 7? pre-coast this register allows the coast signal to be applied prior to the vsync signal. this is necessary in cases where pre- equalization pulses are present. this register defines the number of edges that will be filtered before vsync on a composite sync. the default is 0. 18 7? post-coast this register allows the coast signal to be applied following to the vsync signal. this is necessary in cases where post- equalization pulses are present. this register defines the number of edges that will be filtered after vsync on a composite sync. the default is 0. 19 7? test register must be set to default. 1a 7? test register must be set to 41h for proper operation.
rev. 0 AD9887A ?9 1b 7-0 test register must be set to 00h for proper operation. 1c 7-3 test bits must be set to 0000 0 *** for proper operation. 1c 2 cbcr output order in 4:2:2 mode, the red and blue channels can be inter changed to help satisfy board layout or timing requirem ents, but the green channel must be configured for y. 1c bit 2 controls the order that the u/v(cbcr) data is output. if this bit is high, the red channel data precedes the blue channel data. if this bit is low, the blue channel data precedes the red channel data. see the example in table li. table li. 4:2:2 input/output configuration input channel connection output format red y v/u if 1c bit 2 = 1, u/v if 1c bit 2 = 0 green y y blue u high impedance 1c 1 test bits must be set to 0 for standard input sampling. 1c 0 4:2:2 output mode select 4:2:2 mode can be used to reduce the number of data lines used from 24 down to 16 for applications using yuv, ycbcr, or ypbpr graphics signals. a timing diagram for this mode is shown on page 22. table lii. 4:2:2 output mode select select output mode 1 4:4:4 0 4:2:2 2-wire serial control port a 2-wire serial interface control port is provided. up to four AD9887A devices may be connected to the 2-wire serial interface, with each device having a unique address. the 2-wire serial interface comprises a clock (scl) and a bidirec- tional data (sda) pin. the analog flat panel interface acts as a slave for receiving and transmitting data over the serial inter- face. when the serial interface is not active, the logic levels on scl and sda are pulled high by external pull-up resistors. data received or transmitted on the sda line must be stable for the duration of the positive-going scl pulse. data on sda must change only when scl is low. if sda changes state while scl is high, the serial interface interprets that action as a start or stop sequence. there are five components to serial bus operation: 1. start signal 2. slave address byte 3. base register address byte 4. data byte to read or write 5. stop signal when the serial interface is inactive (scl and sda are high), communications are initiated by sending a start signal. the start signal is a high-to-low transition on sda, while scl is high. this signal alerts all slaved devices that a data transfer sequence is coming. the ? rst eight bits of data transferred after a start signal comprising of a 7-bit slave address (the ? rst seven bits) and a single r/ w bit (the eighth bit). the r/ w bit indicates the direction of data trans- fer, read from (1) or write to (0) the slave device. if the t ransmitted slave address matches the address of the device (set by the state of the sa 1-0 input pins in table liii), the AD9887A acknowledges by bringing sda low on the ninth scl pulse. if the addresses do not match, the AD9887A does not acknowledge. table liii. serial port addresses bit 7 bit 6 bit 5 bit 4 bit 3 bit 2 bit 1 a 6 a 5 a 4 a 3 a 2 a 1 a 0 (msb) 10 01100 10 01101 10 01110 10 01111 data transfer via serial interface for each byte of data read or written, the msb is the ? rst bit of the sequence. if the AD9887A does not acknowledge the master device during a write sequence, the sda remains high so the master can generate a stop signal. if the master device does not acknowledge the AD9887A during a read sequence, the AD9887A interprets this as end of data. the sda remains high so the master can generate a stop signal. writing data to speci ? c control registers of the AD9887A requires that the 8-bit address of the control register of interest be written after the slave address has been established. this control register address is the base address for subsequent write operations. the base address autoincrements by one for each byte of data written after the data byte intended for the base address. if more bytes are transferred than there are available addresses, the address will not increment and will remain at its maximum value of 1dh. any base address higher than 1dh will not produce an acknowledge signal. data is read from the control registers of the AD9887A in a sim ilar manner. reading requires two data transfer operations. the base address must be written with the r/ w bit of the slave address byte low to set up a sequential read operation. reading (the r/ w bit of the slave address byte high) begins at the previously established base address. the address of the read register autoincrements after each byte is transferred. to terminate a read/write sequence to the AD9887A, a stop signal must be sent. a stop signal comprises a low-to-high transition of sda while scl is high. the timing for the read/write operations is shown in figure 37; a typical byte transfer is shown in figure 38. a repeated start signal occurs when the master device driving the serial interface generates a start signal without ? rst generating a stop signal to terminate the current communication. this is used to change the mode of communication (read, write) between the slave and master without releasing the serial interface lines.
rev. 0 ?0 AD9887A bit 7 sda scl ack bit 6 bit 5 bit 4 bit 3 bit 2 bit 1 bit 0 figure 38. serial interface?ypical byte transfer serial interface read/write examples write to one control register: ? start signal ? slave address byte (r/ w bit = low) ? base address byte ? data byte to base address ? stop signal write to four consecutive control registers: ? start signal ? slave address byte (r/ w bit = low) ? base address byte ? data byte to base address ? data byte to (base address + 1) ? data byte to (base address + 2) ? data byte to (base address + 3) ? stop signal read from one control register: ? start signal ? slave address byte (r/ w bit = low) ? base address byte ? start signal ? slave address byte (r/ w bit = high) ? data byte from base address ? stop signal read from four consecutive control registers: ? start signal ? slave address byte (r/ w bit = low) ? base address byte ? start signal ? slave address byte (r/ w bit = high) ? data byte from base address ? data byte from (base address + 1) ? data byte from (base address + 2) ? data byte from (base address + 3) ? stop signal table liv. control of the sync block muxes via the serial register mux serial bus control nos. control bit bit state result 1 and 2 12h: bit 4 0 pass hsync 1 pass sync-on-green 3 12h: bit 1 0 pass coast 1 pass vsync 4 12h: bit 2 0 pass vsync 1 pass sync separator signal 5, 6, and 7 11h: bit 3 0 pass digital interface signals 1 pass analog interface signals theory of operation (sync processing) this section is devoted to the basic operation of the sync pro cess- ing engine (refer to figure 39 sync processing block diagram). sync stripper the purpose of the sync stripper is to extract the sync signal from the green graphics channel. a sync signal is not present on all graphics systems, only those with sync-on-green. the sync signal is extracted from the green channel in a two step process. first, the sog input is clamped to its negative peak (typically 0.3 v below the black level). next, the signal goes to a compara- tor with a trigger level that is 0.15 v above the clamped level. the output signal is typically a composite sync signal containing both hsync and vsync. sync separator a sync separator extracts the vsync signal from a composite sync signal. it does this through a low-pass ? lter-like or integrator- like operation. it works on the idea that the vsync signal stays a ctive for a much longer time than the hsync signal, so it re jects any signal shorter than a threshold value, which is somewhere between an hsync pulsewidth and a vsync pulsewidth. the sync separator on the AD9887A is simply an 8-bit digital counter with a 5 mhz clock. it works independently of the polarity of the composite sync signal. (polarities are determined elsewhere on the chip.) the basic idea is that the counter counts up when hsync pulses are present. but since hsync pulses are relatively short in width, the counter only reaches a value of n before the pulse ends. it then starts counting down eventually reaching 0 before the next hsync pulse arrives. the speci ? c sda scl t buff t dho t dal t dah t dsu t stasu t stosu t stah figure 37. serial port read/ write timing
rev. 0 AD9887A ?1 value of n will vary for different video modes but will always be less than 255. for example with a 1 s width hsync, the counter will only reach 5 (1 s/200 ns = 5). now, when vsync is present on the composite sync, the counter will also count up. however, since the vsync signal is much longer, it will count to a higher number m. for most video modes, m will be at least 255. so, vsync can be detected on the composite sync signal by detecting when the counter counts to higher than n. the speci ? c count that triggers detection (t) can be programmed through the serial register (0fh). once vsync has been detected, there is a similar process to detect when it goes inactive. at detection, the counter ? rst resets to 0, and then starts counting up when vsync goes away. similar to the previous case, it will detect the absence of vsync when the counter reaches the threshold count (t). in this way, it will reject noise and/or serration pulses. once vsync is detected to be absent, the counter resets to 0 and begins the cycle again. pcb layout recommendations the AD9887A is a high performance, high speed analog device. in order to achieve the maximum performance out of the part, it is important to have a well laid out board. the following is a guide for designing a board using the AD9887A. analog interface inputs using the following layout techniques on the graphics inputs is extremely important. minimize the trace length running into the graphics inputs. this is acc omplished by placing the AD9887A as c lose as possible to the graphics vga connector. long input trace lengths are undesirable because they will pick up more noise from the board and other external sources. place the 75 ? termination resistors as close to the AD9887A chip as possible. any additional trace length between the termi- nation resistors and the input of the AD9887A increases the magnitude of reflections, which will corrupt the graphics signal. use 75 ? matched impedance traces. trace impedances other than 75 ? will also increase the chance of reflections. the AD9887A has very high input bandwidth (330 mhz). while this is desirable for acquiring a high resolution pc graphics signal with fast edges, it means that it will also capture any high fre- quency noise present. therefore, it is important to reduce the amount of noise that gets coupled to the inputs. avoid running any digital traces near the analog inputs. due to the high bandwidth of the AD9887A, sometimes low-pass ? ltering the analog inputs can help to reduce noise. (for many applications, ? ltering is unnecessary.) experiments have shown that placing a series ferrite bead prior to the 75 ? termination resistor is helpful in ? ltering out excess noise. speci ? cally, the part used was the # 2508051217z0 from fair-rite, but each application may work best with a different bead value. alternately, placing a 100 ? to 120 ? resistor between the 75 ? termination resistor and the input coupling capacitor can also be beneficial. digital interface inputs each differential input pair (rx0+, rx0 C , rxc+, rxc C , etc.) should be routed together using 50 ? strip line routing techniques and should be kept as short as possible. no other components should be placed on these inputs; for example, no clamping diodes. every effort should also be made to route these signals on a single layer (component layer) with no vias. sync stripper acti vity detect negative peak clamp comp sync sog h sync in acti vity detect mux 2 hsync out pixel clock mux 1 sync separator integrator v sync sog out hsync out vsync out mux 4 vsync in 1/s pll hsync acti vity detect AD9887A clock generator polarity detect polarity detect polarity detect mux 3 coast coast figure 39. sync processing block diagram
rev. 0 ?2 AD9887A power supply bypassing it is recommended to bypass each power supply pin with a 0.1 f capacitor. the exception is in the case where two or mo re s upp ly pins are adjacent to each other. for these group- ings of powers/grounds, it is only necessary to have one bypass capacitor. t he fundamental idea is to have a bypass capacitor within about 0.5 cm of each power pin. also, avoid placing the capacitor on the opposite side of the pc board from the AD9887A, as that interposes resistive vias in the path. the bypass capacitors should be physically located between the power plane and the power pin. current should flow from the power plane to the capacitor to the power pin. do not make the power connection between the capacitor and the power pin. placing a via underneath the capacitor pads, down to the power plane, is generally the best approach. it is particularly important to maintain low noise and good stability of pv d (the clock generator supply). abrupt changes in pv d can result in similarly abrupt changes in sampling clock phase and frequency. this can be avoided by careful attention to regulation, ? ltering, and bypassing. it is highly desirable to pro- vide separate regulated supplies for each of the analog circuitry groups (v d and pv d ). some graphic controllers use substantially different levels of power when active (during active picture time) and when idle (during horizontal and vertical sync periods). this can result in a measurable change in the voltage supplied to the analog supply regulator, which can in turn produce changes in the regulated analog supply voltage. this can be mitigated by regu- la ting the analog supply, or at least pv d , from a different, cleaner power source (for example, from a 12 v supply). it is also recommended to use a single ground plane for the entire board. experience has repeatedly shown that the noise performance is the same or better with a single ground plane. using multiple ground planes can be detrimental because each separate ground plane is smaller, and long ground loops can result. in some cases, using separate ground planes is unavoidable. for those cases, it is recommended to at least place a single ground plane under the AD9887A. the location of the split should be at the receiver of the digital outputs. for this case, it is even more important to place components wisely because the current loops will be much longer (current takes the path of least resistance). an example of a current loop follows. p o w e r p l a n e a d 9 8 8 7 a d i g i t a l o u t p u t t r a c e a n a l o g g r o u n d p l a n e d i g i t a l g r o u n d p l a n e d i g i t a l d a t a r e c e i v e r figure 40. example of a current loop pll place the pll loop ? lter components as close to the filt pin as possible. do not place any digital or other high frequency traces near these components. use the values suggested in the data sheet with 10% tolerances or less. outputs (both data and clocks) try to minimize the trace length that the digital outputs have to drive. longer traces have higher capacitance, which require more current that causes more internal digital noise. shorter traces reduce the possibility of reflections. adding a series resistor with a value of 22 ? C 100 ? can suppress reflections, reduce emi, and reduce the current spikes inside of the AD9887A. however, if 50 ? traces are used on the pcb, the data outputs should not need these resistors. a 22 ? resistor on the datack output should provide good impedance matching that will further reduce refections. if emi or current spiking is a concern, it is recommended to use a lower drive strength setting. if series resistors are used, place them as close to the AD9887A pins as possible (try not to add vias or extra length to the output trace in order to get the resistors closer). if possible, limit the capacitance that each of the digital outputs drives to less than 10 pf. this can easily be accomplished by keeping traces short and by connecting the outputs to only one device. loading the outputs with excessive capacitance will increase the current transients inside the AD9887A creating more digital noise on its power supplies. digital inputs the digital inputs on the AD9887A were designed to work with 3.3 v signals. any noise that gets onto the hsync input trace will add jitter to the system. therefore, minimize the trace length and do not run any digital or other high frequency traces near it. voltage reference bypass with a 0.1 f capacitor. place as close to the AD9887A p in as possible. make the ground connection as short as possible. refout is easily connected to refin with a short trace. avoid making this trace any longer than it needs to be. when using an external reference, the refout output, while unused, still needs to be bypassed with a 0.1 f capacitor in order to avoid ringing.
rev. 0 AD9887A ?3 outline dimensions 160-lead metric quad flatpack package [mqfp] (s-160) dimensions shown in millimeters 0.50 0.25 0.65 bsc 25.35 ref 0.40 0.22 121 160 1 120 40 80 81 top view (pins down) pin 1 41 4.10 max 1.03 0.88 0.73 3.60 3.40 3.20 0.10 min coplanarity seating plane 31.20 bsc sq 28.00 bsc sq compliant to jedec standards ms-022dd-1
c02838??/03(0) ?4

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